Brushless Multiphase Self-Commutation (or BMSCC) And Related Invention

ABSTRACT

Brushless Multiphase Self-Commutation Control (or BMSCC), also known as Real Time Emulation Control (or RTLC), is a contact-less means for powering any electric apparatus with “conditioned” or “re-fabricated” multiphase electrical excitation that is synchronized to the movement of the electric apparatus. BMSCC inherently phase-locks the frequency of excitation to any speed or position of the electric apparatus being controlled by a natural electromagnetic processing means and as a result, the BMSCC is an Electromagnetic Self-Commutator. BMSCC should never be confused with any derivative of Field Oriented Control, which is the other means of conditioning speed-synchronized electrical excitation by iteratively performing “speed-variant-to-speed-invariant” transformations and frequency synthesis by the unnatural processing means of an electronic computer. The control flexibility of BMSCC realizes additional synergistic or complementary electric apparatus inventions as shown in the illustration.

PRIOR ART

U.S. Pat. Nos. 4,459,540; 4,634,950; 5,237,255 and 5,243,268 of this inventor disclosed the “Electric Rotating Apparatus and Electric Machine” system that incorporates an inherent phase-locking means for supplying speed-synchronized, multiphase electrical power to the moving active winding sets of an electric machine entity, which is an electric motor or electric generator, without electrical-mechanical contacts (i.e., brush-less). As disclosed by the aforementioned patents of this inventor, the means for providing speed-synchronized power to the Power Generator Motor (or PGM), which is a Wound-Rotor Doubly-Fed Electric Machine entity or a stator based permanent magnet singly-fed electric machine entity, is a Rotor Excitation Generator (or REG). The REG-PGM combination has not been commercially available because many years of continued research, development, and prototyping by this inventor have shown new inventions that are crucial for practical control and operation. Still, the patents realize the only potential embodiment of a Brushless Wound-Rotor [Synchronous] Doubly-Fed Electric Machine System.

At the time of the “Electric Rotating Apparatus and Electric Machine” patents, this inventor was not familiar with the basic two means of speed-synchronized excitation for electric machines, which are Self-Commutation and derivatives of Flux Oriented Control (or FOC), such as Flux Vector Control (or FVC).

As it names implies, Self-Commutation is an inherent means of instantaneously and automatically commutating, or more appropriately phase-locking, the frequency of the electrical excitation signals of the windings to the speed of the shaft movement for continuous functional operation and acceleration of the electric machine without the necessity of continually intervening the phase-locking means with unnatural processing on an electronic computer. As a result, Self-Commutation is considered an “emulation” means of electric machine speed-synchronization.

Self-Commutation has three traits that distinguish itself from the other speed-synchronizing means for electrically exciting electric machines, such as derivatives of Field Oriented Control (FOC). Trait 1, Self-Commutation will naturally accelerate the electric machine to its mechanical limits “without” the need for continuous intervention by an artificial means of speed detection and feedback control, such as an electronic processor means. Trait 2, Self-Commutation can directly operate on any frequency of Alternating Current (AC), including Direct Current (DC), because the speed-synchronized frequency of excitation is automatically produced (i.e., self-commutation). Trait 3, as its name implies Self-Commutation produces speed-synchronized electrical excitation signals naturally and without electronic synthesis.

The other means of speed-synchronizing the electrical excitation of electric machines is any derivative of FOC. Invented in the early 1970's, FOC could only become what is considered today's most state-of-art electronic excitation control because enormous advances in electronic processing performance and density satisfied the formidable processing complexity of FOC in some situations. FOC always has four “basic” steps in its control process. Step one, the time and speed “variant” system parameters of the electro-mechanical converter (i.e., the torque producing electric machine) are measured to form reference signals. Step two, the reference signals of the multiphase time and speed “variant” system parameters, as referenced to the low frequency magnetic energy of the actual torque producing electric machine, are transformed (sometimes referred to as rotating the reference signals) into a two co-ordinate time and speed “invariant” counterpart (template waveform) by estimation algorithms running on powerful electronic computers. The “speed invariant” two co-ordinates are respectively referred to as the “d” co-ordinate, which is the flux component, and the “q” co-ordinate, which is the torque component. Step three, the d and q co-ordinate values are re-calculated again by electronic computers to achieve the desired response, such as torque, power factor, etc. Step four, the electronic computers use the recalculated d and q co-ordinates to “synthesize” the phase and frequency of the variable, speed-synchronized excitation waveform by an electronic switching inverter under Pulse Width Modulation or Space Vector Modulation. The four basic steps must be “continuously” performed (or re-iterated) for shaft acceleration or and stable electric machine operation. As a result, FOC is considered a “simulation” or “artificial” means of control, because the computations are not instantaneous and the estimation algorithm always deviates from the actual electromagnetic process.

FOC has three distinguishing traits. Trait 1, the resolution of control is asymptotically limited, is closely determined by the power and speed of the electronic computers, and is inherently unstable; particularly, at low excitation frequencies, where measurement and estimation become elusive. Trait 2, without constant reiterative intervention of the process to recalculate the “speed variant” to “speed invariant” transformation and to re-synthesize the excitation waveform by powerful electronic computers, FOC cannot continuously accelerate (or even maintain) the speed of the shaft. Trait 3, FOC must convert input electrical power to an intermediate frequency, such as DC, to support variable frequency synthesis. Further, the high frequency synthesized excitation waveform is directly applied to the low frequency designed active winding set or the multiphase AC power source with detrimental consequences, if not properly compensated for.

Because of the enhanced performance associated with true Self-Commutation, electric machines controlled by any derivative of Field Oriented Control (FOC) are often (and incorrectly) advertised as “self” commutated electric machines as a marketing gimmick.

Prior to the “Electric Rotating Apparatus and Electric Machine” patents of this inventor, Self-Commutation was only available with the venerable DC (or Universal AC) electric machines that incorporate an “Electro-Mechanical” Commutator. The “Electro-Mechanical Commutator” of the so-called DC (or Universal AC) electric machine strategically arranges electro-mechanical switches about the circumference of the rotor shaft that make electrical contact with sliding brushes. The electro-mechanical switches are sequentially activated to direct the flow of “single phase” current through the rotor active winding sets in accordance with the speed and position of the rotating shaft. The current flow changes discretely as the switches make contact. The resolution of control is real estate dependent on the number of switches that can occupy the contact space while being capable of supplying current.

In contrast to electro-mechanical self-commutation, “electro-magnetic” self-commutation uses an arrangement of power semiconductors, called Synchronous Modulator-Demodulators (i.e., Modems), on each side of a Position Dependent Flux High Frequency Transformer (or PDF-HFT). Electromagnetic self-commutation electromagnetically directs the flow of single or multiphase current (or flux) through the winding sets of the PDF-HFT in accordance with the position and speed of the rotating shaft (i.e., electric machine speed-synchronization), which in turn excite the rotor active winding sets of the PGM. The current flow is continuously smooth. The resolution of control is electromagnetic and significantly better than the electromechanical self-commutator.

This inventor now realizes the REG of the “Electric Rotating Apparatus and Electric Machine” patents is one means of “Electro-Magnetic” Self-Commutation and this inventor has since defined several new terms to better describe electro-magnetic self-commutation, which are Rotor Excitation Generation and Rotor Excitation Generator (or REG). Rotor Excitation Generation, which is a synonym for electro-magnetic commutation, is any brushless real time emulation means that generates the precise signal waveforms for exciting a multiphase rotating winding set of an electric machine at any speed. Rotor Excitation Generator is any device that provides Rotor Excitation Generation.

Although U.S. Pat. Nos. 4,459,540; 4,634,950; 5,237,255 and 5,243,268 of this inventor coincidentally disclosed at the time to be the only brushless means of self-commutation for speed-synchronizing the electrical excitation, which was within the REG embodiment of implementing a Brushless Wound-Rotor [Synchronous] Doubly-Fed Electric Machine or a stator based permanent magnet or field winding singly-fed electric machine, the claims of the patents did not understand or disclose peculiar new REG art that could only be learned from additional years of REG motivated research by the inventor while attempting to make the issued patents practical. For instance, the patents disclosed traditional modulation techniques that were understood at the time and successfully used by conventional electronic controllers for speed and torque control of electric machines. The inventor did not realize that these traditional modulation techniques of phase, frequency, and amplitude modulation were not appropriate with the non-conventional REG that incorporates Synchronous Modems on each side of a multiphase High Frequency Rotating Transformer (HFRT). The Synchronous Modems must generate high frequency signals with symmetrically bipolar transitions (or signals without any DC bias) for compatibility with the PDF-HFT. Further, the inventor did not understand the extraordinary environmental stress placed on the electrical and electronic equipment of the issued U.S. patents. For instance, the electrical and electronic components are directly exposed to the harsh environment of the electric machine installation because the issue patents disclose the only electric machine that must closely couple all electrical and electronic components to the moving shaft of the electric machine. Consequently, the issued U.S. patents did not understand or disclose the modulation requirements for Power Factor control and speed-torque control or the environmental requirements for the sensitive electrical and electronic equipment for practical operation of the Electric Rotating Apparatus and Electric Machine.

To best understand the new art of BMSCC and its distinguishing characteristics from pertinent prior art, including aspects of the “Electric Rotating Apparatus and Electric Machine” patents of this inventor, an introduction to electric machines will follow.

Electric Machines are electromechanical converters, which convert electric power to mechanical power or visa-versa. All Electric Machines have one mutually independent port for “mechanical” power, which experiences rotation or linear movement at a given speed and torque (or force), and one port for “electrical” power (i.e., Singly-Fed) or at most two mutually independent ports (i.e., Doubly-Fed) for “electrical” power. More than three mutually independent power ports is a duplication of the Singly-Fed or Doubly-Fed categories of Electric Machines. By pumping an average mechanical power into the mechanical port, the electrical port(s) will output an average electrical power (or generate). By pumping an average electrical power into the electrical port(s), the mechanical port will output an average mechanical power (or motor).

The basic electromagnetic core structure of any electric machine consists of the rotor (or moving) assembly and the stator (or stationary) assembly that are separated by a single air gap to allow relative movement. Electric machine operation can be simply described as two synchronized rotating (or moving) magnetic fields that are on the rotor (or moving body) assembly and the stator (or stationary body) assembly, respectively. Essentially one moving magnetic field drags the other magnetic field (and its associated carrier body) along by magnetic attraction (or repulsion) and thereby, creating work. Without synchronization between the rotating (or moving) magnetic fields on each side of the air gap, torque (or force) pulsation would result and no useful average power could be produced. Since Ampere's Circular Law implies Magnetic Flux and Current are interchangeable terms, rotating (or moving) current sheets show the same analogy as rotating (or moving) magnetic fields. Ampere's Circular Law simply states the Magnetic Flux Intensity along a circular path at a given radius from a current carrying conductor is equal to the Magneto-Motive-Force on the conductor divided by the circumference of the circular path. Magneto-Motive-Force (or MMF) is the product of the number of current carrying conductors (i.e., winding-turns) and the current in the conductors.

-   -   NOTE: Linear (or moving) and rotating electric machines follow         the same electromagnetic principles of operation. As used         herein, “torque” will be used interchangeably with “force” and         “rotating” will be used interchangeably with “moving”, where         “torque and rotating” are terms applied to rotating electric         machines and “force and moving” are terms applied to linear         electric machines.

There are two basic relations that simultaneously govern electric machine operation, Faraday's Law and Lorentz Relation. Faraday's Law simply states that the port Voltage of any electric machine is equal to the change in flux, ψ, over time that cuts through a given number of winding-turns, N. Lorentz Relation simply states that the force (or torque) on a current carrying conductor with a given length is the cross-product between the total current in the conductors and the Magnetic Flux Density, β, which is a direct derivative of Magnetic Flux Intensity, H, and the MMF on the conductor. Lorentz Relation stipulates the direction of force follows the Right-Hand-Rule convention, which shows the force to be perpendicular to the plane of the current and flux axis, and the phase angle between the two synchronized rotating (and moving) fields (or the current and flux axis) must be greater than zero degrees for force to occur with the greatest force occurring at any odd multiple of 90 degrees or π/2 radians. Since current and flux are interchangeable terms, the terms of Lorentz Relation can be purely magnetic or purely current.

Any deviation from the basic electromagnetic core structure or the principle of operation as just described, which is synchronized rotating magnetic fields (or current sheets) on each side of an air gap, is simply a duplication of the basic core structure of the electric machine as describe. For instance, the so-called Dual Mechanical Port Electric Machine (DMP) has two air gaps within the same body and accordingly, it is two basic electric machines in the same body.

A rotating (or moving) magnetic field can be realized by a rotating (or moving) Permanent Magnet Assembly, by a rotating (or moving) “Passive” Winding Set Assembly, or by a stationary or rotating (or moving) “Active” Winding Set Assembly. The “Passive” Winding Set and the Permanent Magnet Assembly have no electrical or mechanical gateway for “real” power production or consumption (other than dissipative power or electrical loss while producing the magnetic field). Consequently, the Permanent Magnet Assembly and the Passive Winding Set Assembly passively participate in the energy conversion process for the sole purpose of satisfying the magnetic field condition of Lorentz Relation and as a result, Permanent Magnets and Passive Winding Sets Assemblies are commonly interchangeable assemblies. Examples of Passive Winding Sets are the AC (i.e., Alternating Current) Squirrel Cage Winding Assembly found in Asynchronous (i.e., Induction) Electric Machines and either the Conventional or Superconductor DC (i.e., Direct Current) Winding Assembly (or Electromagnet) found in Synchronous Electric Machines. In contrast, “Active” Winding Sets experience real (or active) power (other than dissipative power or electrical loss), and as a result, actively participates in the energy conversion process. An Active Winding Set has to be a multiphase AC winding arrangement that is independently excited with a multiphase AC electrical source (i.e., 3-Phase AC, 6-Phase AC, etc.) through its own independent electrical terminals. Since only a multiphase (AC) winding set with an independent means of excitation (i.e., active winding set) functions as an electrical power gateway and only a multiphase AC winding set produces its own rotating (or moving) magnetic field while situated on a stationary body, all electric machines must incorporate at least one multiphase AC winding set or Active Winding Set, which determines the power capacity of the electric machine. The frequency of electrical excitation of the Active Winding Set must be synchronized to the mechanical speed of the electric machine by the following relationship:

${fm} = \frac{{\pm {fs}} \pm {fr}}{P}$

Where:

-   -   fs is the electrical frequency of the AC excitation on the         stator (or primary) winding set (i.e., 60 Hz) and is related to         the speed of the magnetic field in the air-gap;     -   fr is the electrical frequency of the AC excitation on the rotor         (or moving) (or secondary) winding set, which is virtually zero         for Singly-Fed or Permanent Magnet Electric Machines;     -   fm is the mechanical speed (revolutions per second) of the         rotor;     -   P is the number of magnetic “pole-pairs”;

If an electric machine incorporates a winding on each side of the air gap without any permanent magnets, it is fully electromagnetic and shows two components of MMF to satisfy the magnetic coupling (induction) or transformer action between the winding sets; otherwise Faraday's Law would be violated. One component of MMF, which this disclosure calls Magnetizing MMF, produces the air gap flux density, produces reactive (or imaginary) power, and does not contributes to force. The other component of MMF, which this disclosure calls Power MMF, produces force, produces active (or real) power), and does not contributes to air gap flux density. To satisfy the laws of electric machines, the Magnetizing MMF and the Power MMF must be ninety degrees out of phase.

The Winding Set (or the Permanent Magnet assembly) on each side of the air gap of an electric machine must have similar magnetizing Magneto-Motive-Force (or Permanent Magnet Coercivity) to satisfy the induction principles of a transformer (or to avoid permanent magnet demagnetization, which is exasperated by temperature). Magnetizing MMF produces core Flux Intensity (and core Flux Density) depending on the permeability (or magnetic resistance) of the magnetic path. Coercivity has a similar relationship with Permanent Magnets as MMF does with electromagnets. Electromagnets are also referred to as a field-winding or a wound-field set but never an active winding set.

Due to today's energy consciousness, it is becoming customary to complement any electric machine with electronic excitation control for optimum performance. There are only two basic categories of electronic control, Self-Commutation and derivatives of Field Oriented Control (or FOC). Further, today's most efficient electric machines require electronic excitation control for functional operation. These electric machine “systems” are commonly referred to as Adjustable Speed Drives. Some electric machine systems, such as superconductor electric machine systems, require additional support equipment beyond electronic excitation control for functional operation, such as cryogenic refrigeration, etc. Although rarely the case, the contributing effects associated with the cost, efficiency, reliability, and power density of the electronic excitation controller or ancillary equipment for functional operation of the system should always be included when evaluating the overall performance of the electric machine “system”.

All Electric Machines or Electric Machine Systems can be categorized as either Doubly-Fed or Singly-Fed Electric Machine Systems, which indicate the number of “active winding sets” contained within the basic electromagnetic core structure. Whether Doubly-fed or Singly-fed, all Electric Machines can be further categorized as Asynchronous or Synchronous electric machines, which indicate how the synchronized rotating magnetic fields (or current sheets) on each side of the air gap are maintained. Asynchronous Electric Machines “dependently” maintain the two rotating magnetic fields by the mutual induction of current (i.e., the rotating transformer principles) due to a difference in rotational (or moving) speed (i.e., slip) between the Passive AC Winding Set and the rotating field in the air gap. The slip should be kept small for best performance. In contrast, Synchronous Electric Machines “independently” maintain each of the two rotating magnetic fields; the rotor maintains a field by mechanical rotation of the constant magnetic field of a permanent magnet assembly or a field winding assembly. Asynchronous Electric Machines are inherently stable, exhibit startup torque, and can operate standalone on multiphase AC power, because the mutually inclusive maintenance of the two rotating magnetic fields by slip holds synchronism between the two moving magnetic fields regardless of speed. Note: this is not self-commutation because the slip must be continuously maintained by some control means regardless of speed or excitation frequency for continuous acceleration. Synchronous electric machines are inherently unstable, do not exhibit startup torque, and cannot operate standalone, because the mutually exclusive maintenance of the two rotating magnetic fields is prone to loss of synchronism with potentially devastating results.

-   -   Note: Any Electric Machine that independently maintains the         synchronized rotating magnetic fields on each side of the air         gap without the need to maintain slip for speed based induction         even while potentially experiencing slip is considered a         Synchronous Electric Machine. Common examples of synchronous         electric machines are the so-called brushless DC Electric         Machines (i.e., permanent magnet), Field Excited Synchronous         Electric Machines (i.e., electromagnet), Synchronous Reluctance         Electric Machines, and Wound-Rotor [Synchronous] Doubly-Fed         Electric Machines. Examples of Asynchronous Electric Machines         are the Singly-fed Induction Electric Machines (i.e., squirrel         cage rotor, wound-rotor, and slip-energy recovery) and the         Doubly-Fed Induction Electric Machines (or so-called Brushless         Doubly-Fed Electric Machines) with the two active winding sets         having unlike pole-pairs and as a result, rely on rotational         speed based (i.e., slip) induction for excitation.

Wound-Rotor Doubly-Fed Electric Machines have two independently excited active winding sets for the independent production of the two synchronized rotating (or moving) magnetic fields and are therefore synchronous electric machines. At least one active winding set must be excited with bi-directional electrical power. As the only electric machine with an “active” winding set situated on the rotor, the rotor core assembly of the Wound-Rotor Doubly-Fed Electric Machine becomes an “active” participant in the energy conversion process and adds real power to the system. In all other electric machines, the real estate of the rotor core assembly (or in some cases the stator core assembly) is considered underutilized because the rotor is only a passive participant in the energy conversion process and does not add real power to the system. With this consideration, the Wound-Rotor [Synchronous] Doubly-Fed Electric Machine has the most ideal electromagnetic core structure of any electric machine with a given air gap flux density. However, the Wound-Rotor Doubly-Fed Electric Machine incorporates sliding contacts (i.e., multiphase slip ring assembly) for an independent electrical excitation connection to the rotating active winding set and is acutely unstable at synchronous speed, where the frequency and voltage of the rotor excitation is difficult to measure or synthesize by any derivative of FOC electronic control. Together, the multiphase slip ring assembly and the instability impose a formidable “Achilles' Heel” for the Wound-Rotor Doubly-Fed electric machine, which has kept this electric machine in virtual oblivion except as the classic study of electric machines.

Two facts are indisputable among electric machine experts with ample evidence emerging from technical periodicals and research projects, the Wound-Rotor [Synchronous] Doubly-Fed Electric Machine shows twice the constant torque speed range for a given frequency and voltage of operation (7200 rpm@60 Hz, 1 pole-pair) and its electronic excitation controller conditions only the power of the rotor active winding set, which is a fraction (half or less) of the total power of the electric machine. While disregarding its Achilles' Heel, in theory these facts give the Wound-Rotor [Synchronous] Doubly-Fed Electric Machine significant attributes compared to all other electric machines with similar air gap flux densities. Since the two active winding sets conveniently occupy the same physical volume by utilizing the otherwise passive rotor space, the Wound-Rotor [Synchronous] Doubly-Fed Electric Machine shows twice the power density as singly-fed electric machines, assuming all active winding sets have similar ratings. Since the total current is shared between the two active winding sets, the Wound-Rotor [Synchronous] Doubly-Fed Electric Machine shows the same electrical loss (i.e., I²R loss) as the most efficient electric machine available, which is the singly-fed synchronous electric machine with a lossless permanent magnet assembly (i.e., brushless DC electric machine), assuming the permanent magnet assembly produces the same Flux Density as the active winding sets. Likewise, the Wound-Rotor [Synchronous] Doubly-Fed Electric Machine shows nearly half the electrical loss as a similarly rated asynchronous (i.e., induction) electric machine, which must include the additional electrical loss of the “passive” winding set on the rotating body. After legitimately including the significant cost, efficiency, and power density advantages of its electronic controller and disregarding its Achilles' Heel, nothing approaches the Wound-Rotor [Synchronous] Doubly-fed electric machine system (including today's superconductor electric machines), if cost, efficiency, and power density were the principal considerations.

The Wound-Rotor [Synchronous] Doubly-fed Electric Machine, which by extraordinary control means is a doubly-fed synchronous electric machine with two “active” winding sets situated on the stator and rotor, respectively, should never be confused with the “Wound Field” electric machine or the “Wound Rotor” induction electric machine, which by design incorporates only one active winding set. The Wound-Rotor [Synchronous] Doubly-fed Electric Machine and the Wound-Rotor Induction Electric Machine are respective examples of synchronous doubly-fed and asynchronous singly-fed electric machines.

To understand the distinguishing operating features between electric machines, the following qualifying properties of electric machines should be considered.

Chief reason for using permanent magnets in electric machines is to replace brushes or slip rings with purely electronic control, since the moving permanent magnets do not require electrical power. Another reason for using permanent magnets is for improving efficiency, since permanent magnets do not participate in the energy conversion process and do not require or dissipate electrical power. Since permanent magnets do occupy core real estate but do not participate in the energy conversion process, the core real estate of the permanent synchronous electric machine is not optimally utilized as is the core real estate of the wound-rotor doubly-fed electric machine.

Non-Permanent Magnet Electric Machines achieve higher air-gap Flux Density and torque producing current density than a Permanent Magnet Synchronous Electric Machine, if properly designed while disregarding any electrical loss or electrical anomalies associated with achieving the air-gap Flux Density or current density.

Electric Machines incorporate a core of magnetic steel to localize the entire length of the magnetic path through the core to the air gap depth and as a result, the magnetic steel core significantly reduces the MMF requirement of the electric machine. Lower MMF is tantamount to lower electrical loss and higher performance electric machines. Any Flux Density production beyond the core saturation limit requires additional MMF that is based on the low permeability of air, rather than the high permeability of magnetic steel, which is hundreds of times better than air.

The steel magnetic core has its own deficiencies, such as Eddy Current loss and a finite Flux Density saturation limit. To reduce magnetic losses and improve flux density saturation, so-called low loss magnetic steel is traditionally used, which is always improving through constant research on the molecular level, such as nanotechnology and amorphous metals. The core of the electric machine is powdered metal or assembled in layers of magnetic steel (i.e., ribbon, laminations, etc.) to increase the resistance to eddy currents.

Electric machines are further categorized by the direction of the flux through the air-gap. If the flux travels parallel to the shaft, the electric machine is referred to as an axial flux electric machine and has a pancake or hockey puck form-factor. If the flux travels perpendicular to the shaft, the electric machine is referred to as a radial flux electric machine and has a classical cylinder in cylinder form-factor. Sort of a misnomer, a Transverse Flux and Longitudinal Flux electric machine indicates the direction of “current” (not the flux) in relation to movement. The current flow in the longitudinal flux electric machine (the classic electric machine) is perpendicular to the magnetic field while the current flow in the transverse flux electric machines is in the same direction of movement. In Transverse flux electric machines the current term in Lorentz relation for force production, which all electric machines must satisfy, is focused by the core into an additional Flux Density term (i.e., current and flux intensity are interchangeable terms).

The efficiency principle behind Synchronous Singly-fed Electric Machines with a Superconductor Field-Winding is the result of achieving ultra high air-gap Flux Density, which reduces the number of winding-turns and associated electrical loss of the “conventional” active winding set, and is not the result of the low electrical loss associated with the superconductor electromagnet as sometimes assumed; otherwise, Permanent Magnets, which have no electrical loss, could easily replace the Superconductor Field-Winding (i.e., electromagnet) with the same result, as is commonly done for conventional passive winding sets (i.e., Field-Windings, electromagnets, etc.).

For a given voltage and frequency of excitation, the power rating of any electric machine is the sum of the power rating of its “active” winding set(s). Likewise, the electrical loss of any electric machine is the sum of the electrical loss of all winding sets associated with the electric machine, including any “passive” winding sets. Electrical Loss has no comparable meaning unless proportionally associated with the power rating of the electric machine. Electrical loss is based on the product of the current squared and the resistance in the winding set (i.e., I²R) with resistance proportional to number of winding-turns or MMF. The synchronous singly-fed electric machine with a single winding set (i.e., the active winding set) shows nearly half the electrical loss as a similarly rated asynchronous singly-fed electric machine, which must include the additional electrical loss associated with the extra “passive” winding set (i.e., the squirrel cage winding) with a similar MMF as the “active” winding set to satisfy the transformer principles of induction. If all active winding sets in any comparison have similar ratings, a wound-rotor [synchronous] doubly-fed electric machine with two active winding sets (and no passive winding set) would show twice the power output and twice the electrical loss as a synchronous singly-fed electric machine (with only one winding set), which is tantamount to the same electrical loss factor as the synchronous singly-fed electric machine and half the electrical loss factor as the asynchronous singly-fed electric machine.

Since all singly-fed electric machines must incorporate one active winding set, which determines the power capacity and physical size of the electric machine, all singly-fed electric machines are approximately the same physical size for a given voltage, current and magnetic flux of operation. Form factor, construction techniques, etc., which can improve power density, should not be used entirely as a power density metric because virtually all of these techniques can be migrated equally to any electric machine type.

Electric machine experts agree, “wound field”, “field wound” or “field winding” are qualifying terms that refer to a specific type of electric machine winding (i.e., a DC electromagnet) that does not actively participate in the energy conversion process but sets up a constant magnetic field in the air gap, which appears rotating (moving) only by the physical action of rotation or movement. Otherwise, there would be no qualifying reason for using the terms “wound field”, “field wound” or “field winding” to distinguish these windings types from the other winding type that all electric machines must incorporate at least one, which is the multiphase AC winding set or “active” winding set.

Higher speed electric machines always show higher power density. However, high speed singly-fed electric machines require high excitation frequency, which leads to high core loss and higher material cost to mitigate the higher core loss. Consequently, all manufacturers of high speed electric machines have incorporated low loss materials in their machine design, such as thinner laminations, amorphous magnetic metals, etc., as fast as they become feasibly available. The wound-rotor doubly-fed shows twice the constant torque speed range (i.e., 7200 rpm with 2 poles and 60 Hz excitation) as singly-fed electric machines (i.e., 3200 rpm with 2 poles and 60 Hz excitation) and as a result, the wound-rotor doubly-fed electric machine has a higher power density core than a singly-fed electric machine while operating at the grid frequency (i.e., 50 hz, 60 hz, etc).

Electronic controllers of electric machines synthesize the frequency and amplitude of the excitation waveforms with high frequency modulation, such as Pulse Width Modulation or Space Vector Modulation. High frequency modulation exposes the windings and power source of the electric machine to high frequency harmonics, which are detrimental to bearing and winding insulation life. High frequency harmonics also cause high core and electrical loss.

The design of electric machines is straight forward and relies heavily on Faraday's Law, Lorentz Relation, and Ampere's Circular Law. These relations can be simplified into the following:

Voltage = K_(V) × (N × β × LEN_(Airgap)) × DIA_(Airgap) × W_(AirgapFlux); ${\beta = {K_{\beta} \times \frac{\mu}{L_{Circumference}} \times {MMF}}};$ ${{Torque} = {K_{T} \times \frac{Voltage}{W_{AirgapFlux}} \times I_{T} \times P_{pp}}};$ Power = Voltage × I_(T);

Where:

-   -   Voltage Voltage level in relation to neutral of the phase (i.e.,         not Phase-to-Phase Voltage)     -   MMF Magneto-Motive-Force or (N×I_(M));     -   N Number of turns contained in an individual winding coil         arrangement (i.e., winding-turns per magnetic pole). A winding         coil produces a magnetic pole-pair;     -   B Flux Density in the air-gap;     -   I_(M) Current in the winding to produce the air-gap flux (i.e.,         Magnetizing Current);     -   μ Permeability of the flux path;     -   L_(Circumference) Circumference (or length) of the magnetic path         (or ideally, the depth of the air gap with an high permeability         magnetic core);     -   I_(T) Current in the winding that produces electromechanical         conversion (i.e., Torque Current);     -   LEN_(Airgap) Air-gap length;     -   DIA_(Airgap) Air-gap diameter;     -   P_(pp) Number of Pole-Pairs;     -   W_(AirgapFlux) Angular speed of the flux in the air gap, which         is 2·π·Frequency;     -   K_(V), K_(β), K_(T) Factors associated with winding factors,         number of air-gap paths, etc.

A simplified design criterion for any electric machine is as follows:

-   -   Step 1. The Design Specification:         -   Desired Voltage of the electrical source;         -   Desired Frequency of the electrical source;         -   Desired Power or desired Force (or Torque).         -   Desired Flux Density, β, in the air gap, which is within the             core saturation criteria and determines the MMF or             magnetizing current (i.e., not torque current);     -   Step 2. The Design Phase (initially, consider a magnetic core         with very high permeability, which is effectively infinite         compared to air)         -   Determine Torque Current, I_(T), by dividing:             -   Desired Power by Voltage;         -   Determine the factor (N×LEN_(airgap)×DIA_(airgap)) with             desired, β, Voltage, and Frequency substitution in Faraday's             Law. For a given β, Voltage, and Frequency, only three             dimensions of design variation, N, LEN_(airgap),             DIA_(airgap).         -   Re-Iterate the effective terms, N, DIA_(airgap), and             LEN_(airgap) of the factor (N×LEN_(airgap)×DIA_(airgap)) for             the desired form-factor.         -   The effective terms DIA_(airgap) and LEN_(airgap) do not             include construction anomalies, such as slot area, wire             size, etc., which may affect the overall dimensions             significantly.         -   Using the dimensions of the effective terms and desired             Magnetizing Current, I_(M), determine the air-gap depth             (i.e., L_(Circumference)) with

${\beta = {K_{\beta} \times \frac{\mu}{L_{Circumference}} \times {MMF}}};$

OBJECTS OF THE INVENTION

After years of proprietary and solitary research, development, and prototyping by this patentee and inventor, who is the sole keeper of the knowledge base that is not obvious to electric machine experts or engineers since there is no similar art in concept, research, or development, it became evident that the REG of U.S. Pat. Nos. 4,459,540; 4,634,950; 5,237,255 and 5,243,268 of this inventor required other important inventions for practical reality of the system and to heighten the performance provided by the system. Brushless Multiphase Self-Commutation Control (or BMSCC) or Real Time Emulation Control (or RTEC) are terms conceived by the patentee to conveniently describe the culmination of important inventions of the REG for practical excitation and control of electric apparatus and to avoid any confusion with the other means of excitation control, which is any derivative of Field Oriented Control (FOC).

-   -   Note: As used herein, BMSCC (or RTEC) are synonymous terms.

One object of the present invention is to provide a Brushless Multiphase Self-Commutation Controller (BMSCC) that further comprises a subset of the components of the REG, such as the Position Dependent Flux High Frequency Transformer (or PDF-HFT) and the Synchronous Modulators-Demodulators or MODEM(s), but in the embodiment of BMSCC with new modulation or gating means and other synergistic art to condition or re-fabricate the waveforms on each side of the PDF-HFT for adjusting the transfer of excitation power to any electric apparatus for full parametric control and practical operation.

Another object of the present invention is to provide supplemental means in the BMSCC embodiment, such as a Position Independent Flux High Frequency Transformer (or PIF-HFT) in conjunction with the PDF-HFT, for BMSCC compatibility with stationary or rotating (or moving) active winding sets of any type of singly-fed or doubly-fed electric machine, including Reluctance electric machines, Asynchronous electric machines, and Synchronous electric machines. Together, the PDF-HFT in conjunction with the PIF-HFT is referred to as the PDF-HFT+PIF-HFT Combination.

A further object of the present invention is to provide Magnetizing Current Generator means (MCG) for first establishing an oscillating magnetic field (or fields) in the core of the PDF-HFT (or PDF-HFT+PIF-HFT Combination) by flowing an oscillating magnetizing current in the winding or windings of the PDF-HFT (or PDF-HFT+PIF-HFT Combination) at a frequency that is within the design criteria of the PDF-HFT (or PDF-HFT+PIF-HFT Combination) and may be varied during operation at any time.

Still another object of the present invention is to provide a Synchronized Gate (or Modulation) Clock or Clocks (SGC) that is synchronized to the symmetrical bipolar transitions of the oscillating magnetic field (or fields) or derivatives, such as the oscillating magnetizing currents or voltages in the PDF-HFT (or PDF-HFT+PIF-HFT Combination), regardless of any change of the frequency of oscillations. The SGC is a reference for gating (or switching) the Synchronous Modems.

Still another object of the present invention is to gate (or modulate) the Synchronous Modems on the primary and secondary sides of the PDF-HFT (or PDF-HFT+PIF-HFT Combination) in time offset relationship to the Synchronous Gating Clock or Clocks (SGC). The time offset relationship can be varied between any Synchronous Modem for electronic adjustment or re-fabrication of the modulation envelop of the waveform for conditioning the power transfer while the PDF-HFT (or PDF-HFT+PIF-HFT Combination) is with or without movement.

Still another object of the present invention is to gate (or modulate) the Synchronous Modems on the primary and secondary sides of the PDF-HFT (or PDF-HFT+PIF-HFT Combination) in cycle burst density relationship to the SGC at predefined intervals for electronic adjustment or re-fabrication of the modulation envelop of the waveform. The intervals (i.e., frames) or density of the cycle burst lengths (i.e., strings) can be varied between any Synchronous Modem for conditioning the power transfer while the PDF-HFT (or PDF-HFT+PIF-HFT Combination) is with or without movement.

Still another object of the present invention is to share the oscillating magnetic field energy in the core of the PDF-HFT between phase windings of the PDF-HFT by gating (or modulating) the synchronous modems with any combination of time offset relationship or cycle burst density relationship for electronic adjustment or re-fabrication of the modulation envelop of the waveform or for parametric control.

Still another object of the present invention is to provide a derivative of BMSCC with the physical relationship between the primary and secondary bodies of the PDF-HFT in a fixed state regardless of the movement of the electrical apparatus being excited while sharing the oscillating magnetic energy of the PDF-HFT for traditional means of electric apparatus control.

Still another object of the present invention is to provide a mechanical adjustment means between the primary and secondary bodies of the PDF-HFT for simultaneously enhancing the electronic adjustment and re-fabrication control means.

Still another object of the present invention is to provide environmental stress immunity to sensitive electrical and electronic components because the BMSCC is the only electronic control means for electric apparatus that requires placement of sensitive components near the movement of the moving body of the electric apparatus and into the same hostile environment experienced by the electric machine.

Still another object of the present invention is to complement BMSCC with any of the following synergistic art: resonant switching (sometimes called soft switching) means, including means to predict the zero crossing by extrapolating out indeterminate delays, wireless communication means between moving and stator bodies, Speed-Position Resolving means inherent in the multiphase PDF-HFT winding arrangement, Capture, Control, Command, and Communication (CCCC) means, and Process Control Means.

Still another object of the present invention is to provide a rotary phase converter or rotary frequency converter while rotating or moving the moving body of the PDF-HFT (or PDF-HFT+PIF-HFT Combination).

Still another object of the present invention is to provide a stationary phase or frequency conversion by sharing the oscillating magnetic energy between phase windings situated within the core of the PDF-HFT (or PDF-HFT+PIF-HFT Combination).

Still another object of the present invention is to provide any type of singly-fed or doubly-fed electric machine that incorporates BMSCC electric machine means, such as asynchronous, synchronous, and reluctance electric machines, which includes linear, rotating, axial flux, radial flux, transverse flux, induction, permanent magnet, and superconductor electric machines.

Still another object of the present invention is to provide a doubly-fed electric machine that incorporates BMSCC electric machine means with a series winding connection arrangement where each phase winding set of the stator of the electric machine is connected in series with the electrical terminals of a phase port of the BMSCC.

Still another object of the present invention is to provide a doubly-fed electric machine that incorporates BMSCC electric machine means with a parallel winding connection arrangement where each phase winding set of the stator of the electric machine is connected in parallel with the electrical terminals of a phase port of the BMSCC.

Still another object of the present invention is to provide any fixed or variable speed constant frequency (VSCF) Wind Turbine (or Windmill) that incorporates BMSCC electric machine means, which is very different from VSCF Wind Turbines with FOC electric machine means.

Still another object of the present invention is to provide any fixed or variable speed constant frequency (VSCF) renewable prime mover, such as tidal, wave, or active solar, that incorporates BMSCC electric machine means.

Still another object of the present invention is to provide an Enhance Transmission Means (ETM) for connecting multiple electric machines to a prime mover, such as the propeller shaft of any Wind Turbine, that can drive one or more electric machines of any kind for converting the speed of the prime mover to a compatible speed expected of the electric machine shaft and for distributing the power and torque strain across multiple electric machines.

Still another object of the present invention is to provide an ETM for Wind Turbines that incorporate BMSCC electric machine means.

Still another object of the present invention is to provide an Electric Vehicle (EV) power train system that incorporates BMSCC electric machine means for electric motoring and generating (during braking).

Still another object of the present invention is to provide a high frequency single or multiphase AC electric power distribution means for electrically powering the power train of any electric vehicle (EV) with any electric machine.

Still another object of the present invention is to provide an electric vehicle (EV) power steering means by controlling (or differentiating) the torque of any two electric machines, where each electric machine independently powers one of the two wheels that steer.

Obviously, numerous variations and modifications can be made without departing from the spirit of the present inventions. Therefore, it should be clearly understood that the form of the present invention described above and shown in the figures of the accompanying drawings is illustrative only and is not intended to limit the scope of the present inventions.

BRIEF DESCRIPTION OF THE DRAWINGS

Numerous other objects, features, and advantages of the invention should now become apparent upon reading of the following detailed description taken in conjunction with the accompanying drawings in which:

FIG. 1 schematically illustrates a Rotor Excitation Generator (REG) exciting a Power Generator Motor (PGM), which is a Wound-Rotor Doubly-Fed Electric Machine in accordance with this patentee's U.S. Pat. Nos. 4,459,540; 4,634,950; 5,237,255; and 5,243,268. It will be used for demonstrating the concept of Brushless Multiphase Self-Commutation and as a result, the circuit topology is simplified to the point of perhaps being non-functional in real life operation.

FIG. 2 demonstrates the signal flow through the PGM entity as referenced to FIG. 4. FIG. 4 blanks out the REG portion of FIG. 1 to focus on the PGM entity.

FIG. 3 demonstrates the signal flow through the REG entity as referenced to FIG. 5. FIG. 5 blanks out the PGM portion of FIG. 1 to focus on the REG entity.

FIG. 4 focuses on the PGM portion of FIG. 1 to better indicate the signal flow through the PGM entity as referenced to FIG. 2.

FIG. 5 focuses on the REG portion of FIG. 1 to better indicate the signal flow through the REG entity as referenced to FIG. 3.

FIG. 6 portrays all embodiments of new art in accordance with the present invention. FIG. 6 includes Modulation Means, synergistic art, and complementary invention peculiar to the present invention.

FIGS. 6-1 is a magnified view of the upper left corner of FIG. 6.

FIGS. 6-2 is a magnified view of the upper right corner of FIG. 6.

FIGS. 6-3 is a magnified view of the lower left corner of FIG. 6.

FIGS. 6-4 is a magnified view of the lower right corner of FIG. 6.

FIG. 7 portrays the new power waveform conditioning (or re-fabrication) technique in accordance with the present invention, referred to as Compensated Time Offset Modulation (CTOM), which gates the Synchronous Modulators-Demodulators (or MODEM) in time offset relationship to the symmetrical bipolar transitions of the high frequency waveforms that is pre-established by the Magnetizing Current Generator (or MCG).

FIG. 8 portrays the new power waveform conditioning (or re-fabrication) technique in accordance with the present invention, referred to as Compensated Pulse Density Modulation (CPDM), which gates the Synchronous Modulators-Demodulators (or MODEM) in cycle burst density relationship at predefined intervals of the symmetrical bipolar transitions of the high frequency waveforms that is pre-established by the Magnetizing Current Generator (or MCG).

FIG. 9 illustrates a 3-Phase example of the high frequency flux or current vector sharing between phase windings of the Position Dependent Flux High Frequency Transformer (PDF-HFT) on an x-y coordinate system as a result of the new modulation techniques in accordance with the present invention.

FIG. 10 is a perspective photographic view of either the rotating (or moving) or stationary section of the Position Dependent Flux High Frequency Transformer (PDF-HFT) including an assembled sectional view, which incorporates both stationary and rotating sections of the PDF-HFT. FIG. 10 illustrates one embodiment of the PDF-HFT, which is an axial flux (or pancake) design with an air gap junction for non-obstructive movement.

FIG. 11 is a perspective photographic view of either the rotating (or moving) or stationary section of the Position Independent Flux High Frequency Transformer (PIF-HFT) including an assembled sectional view, which incorporates both stationary and rotating sections of the PIF-HFT. FIG. 11 illustrates one embodiment of the PIF-HFT, which is an axial flux (or pancake) design with an air gap junction for non-obstructive movement.

FIG. 12 illustrates an embodiment of the Enhanced Transmission Means (ETM), which is the Flexible Transmission System (FTS) art, for connecting multiple electric machine systems to the prime mover, such as the (propeller) shaft of a wind turbine transmission, while modifying the speed ratio at the shaft of the electric machine systems and distributing the power and torque between multiple electric machine systems.

FIG. 13 illustrates an embodiment of the present invention of a Internal (or Planetary) Transmission System (PTS) for connecting multiple BMSCC electric machine systems to the prime mover, such as the (propeller) shaft of a wind turbine, while modifying the speed ratio at the shaft of the electric machine systems and distributing the power and torque between multiple electric machine systems.

FIG. 14 illustrates an embodiment of the present invention of the Electric Vehicle (EV) power train with all invention related components: the electric machine system means (including BMSCC means), the power assisted steering means, and the High Frequency power distribution bus means.

FIG. 15 illustrates switching component connection to the primary and secondary windings of the high frequency transformer with simplified Push-Pull and Full-Bridge circuit topologies. There are other possible circuit topologies.

DETAILED DESCRIPTION OF THE INVENTION

True Brushless Multiphase Self-Commutation Control (BMSCC) or Real Time Emulation Control (RTEC) is a contact-less means of propagating conditioned or re-fabricated electrical power between relatively isolated bodies while naturally inducing any potential mechanical speed or positional movement between the bodies onto the original electrical waveform by means of an Electro-magnetic Self-Commutator (i.e., electromagnetic computer or rotor excitation generator). True Brushless Multiphase Self-Commutation Control (BMSCC) is a new embodiment of a Rotor Excitation Generator (REG). A Rotor Excitation Generator is any device that provides Rotor Excitation Generation, which is synonymous with electromagnetic self-commutation. Previously, the only example of a REG was a component associated with the Electric Rotating Apparatus and Electric Machine patents of this inventor (U.S. Pat. No. 4,459,530, U.S. Pat. No. 4,634,950, U.S. Pat. No. 5,237,255, and U.S. Pat. No. 5,243,268). BMSCC provides other important inventions and new art not known at the time of the original patents but required for practical reality and heightened performance of an REG and the electric machine system it controls. It should be understood that these new embodiments, inventions, means and new art are the result of years of proprietary and solitary research, development and prototyping by this patentee and the sole keeper of the knowledge base and are not obvious to electric machine experts or engineers nor found in prior art. BMSCC (or RTEC) are synonyms coined by this patentee to conveniently describe the new embodiments of an REG and to avoid any confusion with any derivative of Field Oriented Control (FOC). An electric apparatus complemented with BMSCC is an electric apparatus “system.”

To better understand self-commutation means found in BMSCC art for practical control and operation of electric apparatus and the completion of the electric apparatus “system”, a description of the issued “Electric Rotating Apparatus and Electric Machine” patents of this patentee will follow.

FIG. 1 shows a simple electrical schematic representation of a series connected circuit topology that is the only means available to potentially overcome the Achilles' heel of a Wound-Rotor [Synchronous] Electric Machine System and as a result, the potential realization of a Brushless Wound-Rotor [Synchronous] Electric Machine System that is brushless and stable at any speed. As a simple electrical representation, the schematic makes no attempt to show the Brushless Wound-Rotor [Synchronous] Electric Machine System in physical detail or real life application. The schematic is divided into quadrants. The very top quadrant, which is labeled the Power Generator Motor or PGM 1, includes the PGM stator active winding set portion 11 of the Stator Assembly 4 and the PGM rotor active winding set portion 10 of the Rotor Assembly 3, which are separated by an air gap 17 to allow relative movement. The PGM is the actual wound-rotor doubly-fed electromechanical converter or torque producing electric machine entity and operates at the low line frequency (i.e., 60 Hz, etc.). The very bottom quadrant labeled the Rotor Excitation Generator or REG 2 includes the REG stator winding 12 and electronic portion 9 & 6 of the Stator Assembly 4, the REG rotor winding 13 and electronic portion 8 & 7 of the Rotor Assembly 3, and other associated components of the REG, such as the Switch Synchronizer 7, the Rotor Synchronous Modulator/Demodulator (i.e., Modem) 8, the Stator Synchronous Modulator/Demodulator (i.e., Modem) 9 and the Controller Processor 6. Note: The Rotor Synchronous Modems 8 shows three switch groups S4, S5, S6, which is one switch group per phase of the three phase circuit topology example, and the Stator Synchronous Modems 9 shows three switch groups S1, S2, and S3, which is one switch group per phase of the three phase circuit topology example.

A Synchronous Modem is any circuit that converts (modulates) an original waveform to a carrier frequency waveform with the original waveform as the modulation envelop on top of the carrier frequency (or visa versa for demodulation) by synchronously gating (or switching) the bi-directional flow of electrical current (or voltage) at the carrier frequency. It is reasonable to assume Synchronous Modems will occur in pairs, since a modulated signal medium is generally demodulated (or visa-versa). Only this disclosure recognizes “chopping” is synonymous with gating (or switching) the power and “AC Choppers” is synonymous with Synchronous Modem.

The REG is a unique means to propagate electrical excitation to the PGM rotor winding set in accordance with synchronous operation and without electromechanical contact of any kind (i.e., brushless). Together, the REG stator winding set 12 and rotor winding set 13 make up the multiphase High Frequency Rotating (or Moving) Transformer (HFRT) 14. The far right side quadrant labeled the Stator Assembly 4 includes the stator body portions of both the PGM and REG and associated components. The far left quadrant labeled the Rotor Assembly 3 includes the rotor body portions of both the PGM and REG, which are physically attached and as a result, move with the same speed and position relative to the Stator Assembly 4. As shown in the schematic, the PGM is a Doubly-Fed Wound-Rotor Synchronous Electric Machine because it has an Active Winding Set 10 on its Rotor Assembly 3 and an Active Winding Set 11 on its Stator Assembly 4. An active winding set actively participates in the energy conversion process and could be considered an armature winding set. Following standard electric machine concepts, the stator winding set of the PGM 11 could be replaced with a DC Passive Winding Set or Permanent Magnet assembly. Further, the PGM with a compatible REG could be a linear electric machine with moving bodies rather than rotating bodies.

FIG. 2 describes the electrical signal flow through the PGM for a single Alternating Current (AC) Phase that is accompanied with electrical relationships as a result of electric machine analysis, theory, and empirical verification. The same analysis holds for each of any other AC Phase signals of the multiphase AC port in accordance with their relative phase relationship.

The electrical signal flow analysis through the PGM 1 (very top quadrant 1 of FIG. 4) can be analyzed by cross referencing the circled numbers 15 in FIG. 4 with the circled numbers 15 shown in FIG. 2, starting with (Circled 9) 15 and ending with (Circled 6) 16. The stator AC phase signal (Circled 9) 15, which is at frequency Ws, drives its respective phase winding (Circled 8) of the PGM Stator Winding Set 11. Although separated by an air-gap 17, the Stator and Rotor winding sets are in appropriate proximity for electromagnetic coupling. It follows that the PGM functions as a rotating transformer as well as its primary function, which is an electromechanical energy converter, because of the high air gap Flux Density and mutual inductance, which is due to its low frequency of operation. As a result, the electrical signal(s) on the PGM stator winding set 11 (Circled 8) are induced onto the PGM rotor winding set 10 (Circled 7) with a change in electrical phase angle determined by the mechanical movement of the rotor winding set 10 relative to the stator winding set 11. The electrical frequency of the resulting signal 16 (Circled 6) on the rotor winding set 10 has a mechanical phase, α, and speed, W_(M), component associated with it. To appropriately excite the rotor winding set 10 of the PGM by the REG for synchronous operation, the moving body excitation signal 16 (Circled 6) developed by the REG and the PGM must follow the same dynamic relationship as just discussed.

FIG. 3 describes the electrical signal flow through the REG of a single Alternating Current (AC) Phase that is accompanied with electrical relationships as a result of electric machine analysis, theory, and empirical verification. The same analysis holds for each of any other AC Phase signals of the multiphase AC port in accordance with their relative phase relationship.

The electrical signal flow analysis through the REG 2 (very bottom quadrant 2 of FIG. 5) can be analyzed by associating the circled numbers 5 in FIG. 5 with the circled numbers 5 shown in FIG. 3, starting with (Circled 1) 5 and ending with (Circled 6) 16. Initially, the REG chops (or gates) each phase of the multiphase AC port signal 5 (Circled 1) independently by an AC chopper circuit (Synchronous Modem) with an operating frequency (or carrier frequency) that is at least an order magnitude higher than the AC or DC modulation envelop frequency (i.e., kHz versus tens of Hz). The chopped signal (Circled 2) is an unbiased modulated signal and as a result, each symmetrically bipolar transition through the crossing of the zero current or voltage level of the chopper (or carrier) frequency shows virtually no DC bias (i.e., unbiased modulation). As previously mentioned, the Synchronous Modem on the stator (and rotor) is essentially an arrangement of bi-directional AC power switches that symmetrically oscillates the current flow (or power) through the HFRT by gating the circuit of electrical power switches at a rate that is synchronous to the carrier frequency of the modulation. This modulated carrier frequency signal (Circled 2) drives its respective phase winding (Circled 3) of the HFRT Stator Winding Set. The modulation envelope of the resulting induced phase signal on the rotor body (Circled 4) includes a speed and position component associated with the mechanical movement of the rotor winding set in relation to the stator winding set. This modulated carrier frequency signal (4) passes through the rotor Synchronous Modem (Circled 5). Since the Rotor and Stator Synchronous Modems gate synchronously with the carrier frequency, the signals are synchronously demodulated, resulting in only the modulation envelope 16 (Circled 6) remaining. Since the rotor and associated multiphase winding set of the HFRT are attached to the rotor and associated winding set of the PGM, both move at the same speed or position and experience the same electromagnetic and mechanical dynamics. As a result, the demodulated envelop of the REG signals 16 (Circled 6) shown in FIG. 3 has the same electrical frequency and wave relation as the PGM signals 16 (Circled 6) shown in FIG. 2 regardless of speed. It follows the REG signals 16 (Circled 6) shown in FIG. 3 can be directly applied as excitation to the respective phase winding of the PGM 16 (Circled 6) shown in FIG. 1 for speed-synchronized excitation. Each of the other phases will experience the same result in accordance with its appropriate phase shift.

As shown in FIG. 1, the REG, which is virtually unknown to electric machine experts and engineers, brings together a combination of preliminary requirements for stable and brushless Self-Commutation control of the Wound-Rotor Synchronous Doubly-Fed Electric Machine that has continued to elude electric machine experts as is constantly reminded by past, present, and ongoing doubly-fed electric machines research. The preliminary requirements are: 1) “Self-Commutation” or the inherent and instantaneous translation of multiphase AC signals with any excitation frequency to a speed-synchronized multiphase AC signal that is without any process disrupting steps associated with “Non-Self-Commutation” or derivatives of Field Oriented Control (FOC). In contrast, Non-Self-Commutation continually intervenes the process to electronically measure and compute the “speed variant” to “speed invariant” transformation” and again, to electronically “synthesize” the speed-synchronized excitation waveform; 2) the propagation of multiphase electrical power across the air-gap without electromechanical contact (i.e., brushless); 3) the even distribution of currents and voltages over the entire excitation waveform; 4) the natural mitigation of undesired disturbances; 5) the isolation of high frequency signals from low frequency components, such as the power source or the PGM windings; and 6) the inherent potential of soft switching (i.e., resonant switching), which includes the possibility of adding capacitive or inductive reactance for conditioning the slope of the switching edges.

Note: As used herein, soft switching and resonant switching are synonymous.

Inventions and New Art: The REG is the only Brushless Multiphase Electromagnetic Self-Commutation (or MESC) means available. It operates in a similar fashion to the only other example of true Self-Commutation, which is the “electro-mechanical” self-commutated DC (or AC Universal) electric machine. As a result, the REG will naturally accelerate the rotating body of the PGM to its mechanical limit when electrically excited with AC of virtually any frequency, including DC or zero frequency. Only after years of research, development, and prototyping beyond the issued “Electric Rotating Apparatus and Electric Machine” patents of this patentee, this patentee realized that the REG needed other inventions with synergistic art for practical reality and heightened performance of the REG and the electric machine system, which is now provided by the Brushless Multiphase Self-Commutated Control (BMSCC) or Real Time Emulation Control (RTEC) embodiment.

FIG. 6 shows all embodiments and new art of this invention, which is referred to as the Brushless Multiphase Self-Commutation Controller (BMSCC) or similarly referred to as the Real Time Emulation Controller (RTEC) for convenience. Briefly, the new embodiments that are “peculiar” to BMSCC or RTEC are the Electric Apparatus 1, which is any type of Doubly-Fed or Singly-Fed Electric Machine Entity, the Multiphase Electromagnetic Self-Commutator 2 (or Electromagnetic Computer) that is either a new embodiment of the Rotor Excitation Generator (REG) or a Stationary Excitation Generator (SEG), depending on the category or type of electric apparatus being excited, with the distinguishing Modulation Control Means 22 and Synergistic Art 23, which may be duplicated in some way on the primary 18 and secondary sides 19 of the BMSCC. The Electric Apparatus 1 is still referred to as PGM for convenience. Other complementary Inventions 43 conceived during years of research, development, and prototyping are the Dependent Inventions of BMSCC 44 and Independent Inventions of BMSCC 45.

-   -   Note: The PGM (or Power Generator Motor) could be any “electric         apparatus” that needs conditioned multiphase speed-synchronized         electrical power and does not necessarily have to be only         electric machines (i.e., electric motors or generators).

The REG and SEG consist of the Position Dependent Flux High Frequency Transformer (or PDF-HFT) 21, which is embodied in the REG, or the PDF-HFT complemented with a Position Independent Flux High Frequency Transformer (or PDF-HFT+PIF-HFT Combination) 21, which is embodied in the SEG, the Primary 9 and Secondary 8 Synchronous Modems, which are represented by an array of switch symbols having only symbolic relationship to any actual power switch circuit, and the integral Primary 6 and Secondary 7 Controller means.

The culmination of distinguishing art that is “peculiar” to RTEC or BMSCC includes new Modulation Means 22 and Synergistic Art 23 on the stationary side 18 or the rotational (or moving) side 19 or both sides. The Wireless Communication Means (WCM) 20, the Magnetizing Current Generator (or MCG) 24 for implementing Compensated Time Offset Modulation (or CTOM) 25, Compensated Pulse Density Modulation (or CPDM) 26, any combination of CTOM or CPDM 27 and High Frequency Magnetic Energy Sharing (HFMES) means 28, the Simultaneous Mechanical Adjustment Control (SMAC) 29, the Environmental Stress Immunity Means (ESIM) 30, the Basic Three Step Process Control Means (BTPCM) 31, the RTEC (or BMSCC) Synchronization Means (RSM) 32, the Capture, Control, Command, and Communication Processor (CCCC) 33, the Speed/Position Resolving Means (SPRM) 34, and the Soft Switching Compensation Means 35.

Other new Dependent Inventions 44 of the complementary inventions 43 discovered during the research, development, and prototyping of RTEC or BMSCC, which depend on RTEC or BMSCC are: Any Singly-Fed or Doubly-Fed Electric Machine System that uses RTEC or BMSCC 36, Variable Speed Constant Frequency (or VSCF) Wind Turbine (or any Prime Mover such as Renewable Energy) that uses RTEC or BMSCC 37, any Electric Vehicle (EV) Power Train with RTEC or BMSCC 38, and Stationary or Rotary Phase or Frequency Converter, or Pole-Pair Emulator Converters based on BMSCC 39. Any Singly-Fed or Doubly-Fed Electric Machine that uses RTEC (or BMSCC) 36 would include electric generators, electric motors, superconductor electric machines, rotary converters, Pole-Pair Emulator, etc., that use RTEC (or BMSCC) technology.

Other new Independent Inventions 45 of the complementary inventions 43 discovered during the research, development, and prototyping of RTEC or BMSCC: Any EV power train with High Frequency Power Distribution Means (HFPDM) 40, which may or may not include BMSCC (or RTEC), any EV with Dual Electric Machines Power Assistive Steering (DEMPSA) 41, which may or may not include BMSCC, and any VSCF Wind Turbine with the Enhanced Transmission Means (or E™) 42, which may or may not include BMSCC.

-   -   Note: It should be understood that electronic and electrical         circuit arrangements and configurations, electronic and         electrical component arrangements and configurations, winding         arrangements and configurations, mechanical arrangements and         configurations, manufacturing and construction techniques, and         new material and science for implementing all embodiments of         means, synergistic art, and inventions for BMSCC (or RTEC) are         numerous in nature and cannot change the essence of this         invention. Since there is no prior art of BMSCC, all up-to-date         or new science or art of said arrangements and configurations         can only be an extension of said means, synergistic art, and         invention of BMSCC.

REG Art: See the Rotor Excitation Generator or Stationary (Static) Excitation Generator 2 of FIG. 6. A first new embodiment of the Rotor Excitation Generator (REG) comprises Synchronous Modems situated on the primary side (i.e., stationary side) 5 and secondary side (i.e., rotating (moving) side) 8 of a Position Dependent Flux High Frequency Transformer (PDF-HFT) 21 and incorporates new Modulation Control Means 22 and new Synergistic Art 23 of Real Time Emulation Control (RTEC) or Brushless Multiphase Self-Commutation Control (BMSCC). Under this new embodiment, the REG may have at least one junction of movement 17, if an air gap junction is incorporated into the PDF-HFT for free movement between the primary or secondary side of the PDF-HFT (or REG) with associated components. If the REG is allowed to rotate or move with the movement of the electric apparatus, an angular velocity (speed) and phase waveform component is inherently and instantaneously established on to the modulation envelop of the electrical phase signals of the secondary side terminals in accordance to the relative movement or position as viewed from the primary side terminals of the REG including any fabricated waveform component established on the primary side signals as a result of BMSCC Modulation Control Means and Synergistic Art. As an example with this embodiment, the REG brushlessly delivers speed and phase synchronized excitation signals with any number of phases automatically from “Stationary-Side” to the “Moving-Side”, which are signals ideally suited for exciting rotating (or moving) active winding sets of electric machines with excitation waveforms that are synchronized to the speed of the REG shaft, such as for exciting the rotating (or moving) active winding sets of a Wound-Rotor Doubly-Fed Electric Machine.

In another embodiment, an REG is not allowed to rotate or move with the movement of the electric apparatus and the PDF-HFRT may be without an air gap junction. In this embodiment any additional waveform component is re-fabricated waveform components as a result of BMSCC Modulation Control Means and Synergistic Art sharing the oscillating magnetic energy between phase windings of the PDF-HFRT.

SEG Art: See the Rotor Excitation Generator or Stationary (Static) Excitation Generator 2 of FIG. 6. A second new embodiment of the Rotor Excitation Generator (REG) is more appropriately referred to as the Stationary (or Static) Excitation Generator (or SEG). The Stationary (Static) Excitation Generator (SEG) comprises a Position Dependent Flux High Frequency Transformer (PDF-HFT) 21 and a Position Independent Flux High Frequency Transformer (PIF-HFT) 21. The number of secondary phase windings of the PDF-HFT equal the number of secondary phase windings of the PIF-HFT. Each secondary phase winding of the PDF-HFT connect with one phase winding of the secondary windings of the PIF-HFT perhaps on a phase-to-phase basis and the entire combination is referred to as the PDF-HFT+PIF-HFT Combination 21. The Stationary (Static) Excitation Generator (SEG) further comprises Synchronous Modems situated on the primary sides 5 and secondary sides 8 of the PDF-HFT+PIF-HFT Combination 21 and incorporate the new Modulation Control Means 22 and Synergistic Art 23 of Real of Time Emulation Control (RTEC) or Brushless Multiphase Self-Commutation Control (BMSCC). Under this new embodiment, the SEG may have at least two junctions of movement, if an air gap junction is incorporated in both the PDF-HFT and the PIF-HFT of the PDF-HFT+PIF-HFT Combination for free movement between the primary and secondary sides of the PDF-HFT+PIF-HFT Combination. If the SEG is allowed to rotate (or move) with the movement of the electric apparatus, an angular velocity (speed) and phase waveform component is inherently and instantaneously established on to the modulation envelop of the electrical phase signals at the secondary side terminals of the PDF-HFT+PIF-HFT Combination in accordance to the relative movement or position as viewed from the primary side terminals of the SEG including any fabricated waveform component established on the primary side signals as a result of BMSCC Modulation Control Means and Synergistic Art. As an example with this embodiment, the SEG brushlessly delivers speed and phase synchronized excitation signals of any number of phases directly from “Stationary-Side” to the “Stationary-Side”, which is ideally suited for exciting stationary active winding sets with excitation waveforms that are synchronized to the speed of the SEG shaft, such as exciting the stationary active winding set of all types of electric machines, including Permanent Magnet synchronous electric machines, squirrel cage induction electric machines, Reluctance electric machines, so-called Induction Doubly-Fed Electric Machines, and all other Singly-Fed electric machines. For instance, if the SEG is exciting an induction machine, the input frequency to the PDF-HFT+PIF-HFRT Combination may be the desired slip frequency and if the SEG is exciting a DC machine, the input frequency to the PDF-HFT+PIF-HFRT Combination may be DC.

-   -   Note: It should be understood that any new embodiment or art as         a result of RTEC (or BMSCC) is adaptable to both the REG and         SEG. Further, the REG and SEG can support DC electrical power         sources, single phase AC electrical power sources, or multiphase         AC electrical power sources. As used herein, REG and SEG are         interchangeable terms, since the distinguishing difference         between the REG and SEG is the PIF-HFT component of the         PDF-HFT+PIF-HFT Combination 21, as described.

PDF-HFT Art: See the PDF-HFT or PDF-HFT+PIF-HFT Combination 21 of FIG. 6. The Position “Dependent” High Frequency Transformer (PDF-HFT) is designed to change, re-distribute, or share the magnetic flux energy between all phase windings on opposite sides (i.e., the primary side and the secondary side) as a function of movement or position. To allow non-obstructive movement (or positioning), the primary and secondary sides would be separated by at least one air gap. Also, an air gap may be incorporated to more evenly distribute the flux density throughout the core of the transformer. While re-distributing the high frequency magnetic flux energy in the core of the PDF-HFT as a result of movement (or positioning), the PDF-HFT automatically and instantaneously induces the angular velocity (speed) and phase (position) component of the movement onto any excitation signal waveform at its winding terminals while propagating electrical power across its air gap. Therefore, the winding sets of the PDF-HFT with any number of phase windings are physically arranged about the air gap area so any relative movement (or positioning) between the Primary (or stationary) and secondary (or moving) sides will vary the state of the magnetic flux cutting the phase winding sets, such as varying the physical area (or length) of the magnetic path cutting the phase winding sets. One way to accomplish this is to evenly distribute (or balance) and overlap each of the AC phase windings according to phase angle along a plane that is perpendicular to the magnetic path. This is a similar action experienced by electric machines (or the PGM) and as a result, the PDF-HFT follows the same operating principles as described for the PGM or HFRT as a result of movement or positioning between the primary and secondary phase windings. Any signal seen on the rotation (or moving) side of the PDF-HFT will include a mechanical speed and phase component as referenced to any signal waveform on the stationary side (or visa-versa) with a step-up, step-down, or neutral magnitude multiplication as a result of the winding-turns ratio (transformer ratio). The flux path of the PDF-HFT can be a radial magnetic field path (cylindrical form factor) or an axial magnetic field path (pancake or hockey puck form factor) as referenced to the axis of rotation (or movement) of the shaft or even a transverse flux path design. The PDF-HFT can be symmetrical with the same numbers of phase windings between the rotor and stator sides or asymmetrically with a different numbers of phase windings between the rotor and stator sides. The PDF-HFT can be designed for linear movement or rotational movement because the same electromagnetic theory applies.

FIG. 10 shows one embodiment of the PDF-HFT in 3-dimensions 9 d with an isometric equivalency 10 d. This embodiment of the PDF-HFT includes an air gap 2 d for non-obstructive rotation (or movement) about its annulus and for even distribution of the flux density. It is an axial flux design (or pancake form factor) because the flux direction 6 d is perpendicular to the face (as shown) or parallel to the axis of rotation (or annulus 11 d). One half of the PDF-HFT core 1 d has radial winding slots 7 d, 3 d, 8 d on its face filled with a crude representation of almost one winding-turn 4 d of one phase with two pole-pairs. In actuality, there may be more turns per pole or more pole-pairs. Additional phases may include separately excited windings that meet the phase criteria. For this specific example, each of the three windings of a 3-Phase PDF-HFT would be spaced 120 degrees apart or the phase winding 4 d as shown would be rotated by one slot for each of the other phase windings. Therefore, Phase-1 winding may start at slot 7 d (as shown), Phase-2 winding may be a duplicate of Phase-1 winding but may start at slot 8 d, and phase 3 winding may be a duplicate of Phase-1 winding but may start at slot 3 d. The magnetic flux 6 d flows through the air gap 2 d in an axial direction or parallel to the axis of rotation (and perpendicular to the plane of the overlapped phase windings) and this embodiment would be considered a pancake or axial flux core design. Two like pancake winding cores 1 d and 5 d are placed face to face in proximity to each other separated by an air gap 2 d as shown in the isometric drawing. It should be understood that any relative movement between 1 d and 5 d changes the flux path area through the magnetic poles of each of the phase windings, since the plane of the overlapping phase windings is perpendicular to the flux path. Magnetic pole-pairs of the windings are included in the air gap area dynamics of the PDF-HFT, because magnetic pole-pairs occur along the air gap area or in the case of the pancake design, the windings (and pole-pairs) are overlapped on a plane that is perpendicular to the magnetic flux path and as a result, the magnetic flux area changes with movement; hence, the position dependent flux high frequency rotating transformer.

In general, the form factor, pole-pair count, and phase number of the winding sets on each side of the PDF-HFT should be similar to the respective form factor, pole-pair count, and phase number as on the excited electric machine (or PGM) in order to “emulate” the respective excitation waveforms supplied to the PGM by the BMSCC system, regardless of speed. More importantly, the only constraint on the winding arrangement and form factor and excitation of the PDF-HFT is to deliver signals at the moving body with modulated waveforms that duplicate the modulation envelops or “emulate” the form and frequency of the magnetic field or excitation signals expected by the PGM for synchronous operation or electric apparatus.

The PDF-HFT can have any ratio between the number of winding-turns on the secondary (rotor or moving body) and primary (stator body) according to design, such as any step-up, step-down ratio, including neutral ratio. Since the PDF-HFT is designed for much higher frequencies of operation, the number of winding turns and the air gap area of the PDF-HFT would meet the operational requirements of the high frequency carrier and as a result, air gap area and winding turns would be different from the emulated PGM.

Since a linear (moving) electric machine follows the same electromagnetic principles as a rotating electric machine with a similar winding arrangement unrolled or laid out in a linear fashion, the PDF-HFT (or BMSCC system) can support both linear and rotating electric machines by designing to linear or rotating form-factors.

The PDF-HFT could be a balanced phase winding electrical device with the phase windings on the stationary or primary side arranged in accordance with the phase offset (or phase angle) of the AC multiphase signal (i.e., 120 degrees apart for 3-Phase AC) with the magnetic signature between phase windings equal (i.e., the same winding-turns, the same magnetic path, etc). Under this configuration, any imbalance between phase windings, which is a natural reality, may be overcome by individually adjusting the current through the windings by the BMSCC to compensate for the imbalance.

PIF-HFT Art: See the PDF-HFT or PDF-HFT+PIF-HFT Combination 21 of FIG. 6. In contrast to the PDF-HFT, the Position “Independent” Flux High Frequency Transformer (PIF-HFT) does not change, re-distribute, or share any magnetic flux energy between unlike phase windings on the primary and secondary sides, even in accordance with position or movement, which is a dissimilar action experienced on the PGM (or PDF-HFT). The PIF-HFT will only couple magnetic flux energy between primary (stationary) and secondary (moving) windings of the same phase in accordance to winding turns-ratios. An air gap junction may be incorporated for free movement between the primary and secondary sides of the PIF-HFT or for even distribution of flux. For example, a 3-Phase PIF-HFT is essentially three independent transformers integrated into the same body and as a result, PIF-HFT does not induce any angular velocity (speed) and phase waveform component onto any excitation signal at its winding terminals while propagating electrical power across its air gap. Further, varying the current through any phase winding primary and secondary pair will not affect the current through the other phase windings. Therefore, the winding sets of the PIF-HFT with any number of phases are physically arranged about the air gap area so any relative movement between the stationary and moving bodies on each side of the air gap will not vary the magnetic flux path cutting the winding sets. One way to accomplish this is to position the phase windings so the phase winding from unlike phase windings are isolated from each other by not overlapping or occupying the same area along a plane that is perpendicular to the flux path. Consequently, the number of pole-pairs and other position or movement dependent behavior peculiar to the PDF-HFT (and PGM) are not associated with the PIF-HFT. Any signal seen on the stationary side of the PIF-HFT should be similar to any signal seen on the moving side (or visa-versa) regardless of mechanical movement but with a step-up, step-down, or neutral magnitude multiplication as a result of the winding-turns ratio (transformer ratio). The flux path of the PIF-HFT can be radial magnetic field form factor (cylindrical) or axial magnetic field form factor (pancake) or even a transverse flux path design. The PIF-HFT must have the same number of phases on the moving and stationary sides and cannot be asymmetrically, since there is no magnetic coupling between phase windings of unlike phases. To minimize or alleviate inductive cross-talk between PIF-HFT phase winding sets, there may be an air-gap (or high reluctance) means separating each phase winding pair of like phases. The PIF-HFT can be linear (moving) or rotating because the same electromagnetic theory applies.

FIG. 11 shows one embodiment of the PIF-HFT in 3-dimensions 9 e with an isometric equivalency 10 e. Again the 3-dimensioned FIG. 11, which is one-half the PIF-HFT core, shows a pancake style of the PIF-HFT because the flux 6 e flows through the air gap 2 e in an axial direction or parallel to the axis of rotation (or annulus 11 e). Phase Winding slots 3 e, 4 e, and 5 e for the 3-Phase PIF-HFT are ring winding slots on the face of the one-half core and are symmetrically spaced around the axis of rotation. The two cores 1 e and 7 e are placed face to face as shown in the isometric view 10 e, separated by the air gap 2 e. The magnitude of the flux path between the two cores 1 e and 7 e does not change as a result of rotation (or movement). Further, the same flux path is maintained between the same primary and secondary phase winding pair, regardless of movement. Unlike the PDF-HFT, the PIF-HFT has no concept of winding magnetic pole pair because the air gap dimensions of the PIF-HFT does not change in accordance with movement. The number of winding-turns or the air gap area between phases may be designed differently to mitigate anomalies associated with the different diameters of the circular phase winding arrangements.

Unlike the PDF-HFT, the PIF-HFT is not a balanced phase winding device because each “coupled” phase winding set on the stationary or primary side is mutually exclusive from any other coupled phase winding set. Regardless, the magnetic signature between any “coupled” phase winding set should be equal (i.e., the same winding-turns, the same magnetic path, etc). Any imbalance between coupled phase winding sets, such as due to construction reality, may be overcome by individually adjusting the current through the windings by any combination of CTOM or CPDM.

The PDF-HFT and PIF-HFT Combination Art (PDF-HFT+PIF-HFT Combination) See the PDF-HFT or PDF-HFT+PIF-HFT Combination 21 of FIG. 6. The combination of the PDF-HFRT and PIF-HFT, which is a functional ingredient of the SEG, requires both the PDF-HFT and PIF-HFT transformers to have the same number of phase winding sets on the secondary bodies, which are the rotating (or moving) bodies, because the electrical terminals of the secondary phase winding sets are directly connected in accordance with the phase designation (i.e., phase-to-phase). As a result, any mechanical speed, position, or phase waveform component induced on the PDF-HFT secondary winding sets by possible movement or positioning is propagated to the primary side of the PIF-HFT without change (with the exception of any wind-turns ratio amplification). Since the PIF-HFT can only be phase symmetrical, the number of phases on the primary side of the PIF-HFT is equal to the number of phase windings on the secondary side of the PIF-HFT, which is equal to the number of phase windings on the secondary side of the PDF-HFT. However, the PDF-HFT+PIF-HFT Combination can be phase symmetrical or phase asymmetrical as a result of the PDF-HFT.

-   -   Note: As used herein any reference to PDF-HFT equally applies to         the PDF-HFT+PIF-HFT Combination, unless explicitly noted         otherwise.     -   Note: As used herein any reference to PDF-HFT, PIF-HFT, or         electric machine, the secondary side refers to the potentially         moving (or rotating) side and the primary side refers to the         non-moving side.     -   Note: As used herein any reference to PDF-HFT+PIF-HFT         Combination, the primary side of the PDF-HFT+PIF-HFT Combination         is the primary side of the PDF-HFT and the secondary side of the         PDF-HFT+PIF-HFT Combination is the primary side of the PIF-HFT.         However it should be understood that by interchanging the         placement of the PDF-HFT and PIF-HFT relative to each other, the         primary side of the PDF-HFT+PIF-HFT Combination could be the         primary side of the PIF-HFT and the secondary side of the         PDF-HFT+PIF-HFT Combination could be the primary side of the         PDF-HFT.

Winding Form-Factor Art: The Winding Form-Factor determines the winding slot arrangement, the placement of the windings, etc., and as a result, the Winding Form-Factor determines the current density and the effective core flux density of the magnetic core of the electric machine entity (i.e., the PGM), the PDF-HFT, or the PDF-HFT+PIF-HFT Combination. There are many variations of winding form-factors in the industry. Winding Form-Factors, which have been used in the past, have been reconsidered new inventions or art for specific types of electric machines. Because any RTEC or BMSCC controlled electric machine is unknown to electric machine experts or engineers, this invention will incorporate any improved Winding Form-Factors that are relevant to the design of the PDF-HFT, the PDF-HFT+PIF-HFT Combination, or the PGM controlled by BMSCC and will consider these means as new BMSCC or RTEC invention or art.

Magnetic Techniques Art: It has been discussed that all electric machines have at least one Active Winding Set. With two active winding sets being the maximum allowed without electric machine category duplication, the sum of the active winding sets determines the power capacity (i.e., rating) of the electric machine. Consequently, the physical size difference between any singly-fed electric machine with a given voltage and air gap flux density is predominantly determined by the manufacturing, construction, winding form-factor, or magnetic core and conductive material incorporated and less determined by the type of singly-fed electric machine, such as reluctance, asynchronous, or synchronous, as some electric machine experts may suggest. This is true for Wound-Rotor Doubly-Fed Electric Machines as well but Wound-Rotor Doubly-fed Electric Machines already have double the power output advantage compared to Singly-fed Electric Machines because it incorporates two independent active winding sets in virtually the same core volume. Because any RTEC or BMSCC controlled electric machine is unknown to electric machine experts or engineers, this invention will incorporate any manufacturing, construction, or magnetic core material techniques that improve the performance of the PDF-HFT, the PDF-HFT+PIF-HFT Combination, or the PGM controlled by BMSCC and considers these techniques as new BMSCC or RTEC invention.

Modulation Art: See Modulation Means Peculiar to BMSCC or RTEC block 22 of the Primary Controller 6 & 19 and Secondary Controller 7 & 18 of FIG. 6. All conventional Electronic Controllers of Electric Machines modulate the gating of an array of power switches to synthesize the frequency of electrical excitation at the winding terminals (port) of the electric machine, which is a function of speed and position of the electric machine shaft (i.e., the synchronous speed relation), and for controlling the power quality and quantity of the electrical excitation at the electrical terminals of the electric machine. Modulation techniques used by conventional electronic controllers, such as Pulse Width Modulation (PWM), Space Vector Modulation, Phase Modulation, or Frequency Modulation, synthesize the waveform by directly driving the terminals of an electric machine with high frequency modulation while adjusting the high frequency carrier signal, which is greater than one kHz, with a modulation bias (i.e., common mode) that is based on the low frequency required by the electric machine, which is less than 60 Hz. By the principles of PWM, Phase Modulation, Frequency Modulation, etc., for electric machine control, the high frequency carrier signal is asymmetrical to the zero level base line and as a result, always contain some level of DC bias, which maintains the envelope average of the low frequency modulation. These modulation techniques were understood by this patentee at the time to be appropriate modulation techniques for electric machines and therefore, considered the modulation techniques for the Rotating Apparatus and Electric Machine patent numbers (U.S. Pat. No. 4,459,530, U.S. Pat. No. 4,634,950, U.S. Pat. No. 5,237,255, and U.S. Pat. No. 5,243,268). It was learned after years of research, development, and prototyping by this patentee, conventional modulation techniques are inherently incompatible with the electrical power transfer requirements of Real Time Emulation Control (or Brushless Multiphase Self-Commutation Control), which is the only method that controls the transfer of power to the ports of an electric machine by at least controlling the power between the primary-secondary junction of a Position Dependent Flux High Frequency Transformer (i.e. the PDF-HFT). Signals with any level of DC bias, such as those synthesized by Pulse Width Modulation (PWM), Space Vector Modulation, Phase Modulation, or Frequency Modulation for electric machine control, are incompatible with conditioning power propagated through a high frequency transformer, such as the PDF-HFT. The modulation techniques about to be discussed are the results of proprietary research, development, and prototyping by this inventor and cannot be obvious to electric machine control experts or engineers.

FIG. 15 shows at least two circuit topologies for implementing the Modulation Art. The circuit topologies illustrate only one phase of the high frequency transformer for simplicity. One circuit topology is a Push-Pull 1 i arrangement of bi-directional switches (S1, S2, S3, & S4) 5 i connected to and in series with the secondary and primary windings of one phase of the high frequency transformer 3 i, which is centered-tapped 4 i. Another circuit topology is a Full Bridge 2 i arrangement of bi-directional switches (S1A, S1B, S2A, S2B, S3A, S3B, S4A, & S4B) 8 i connected to and in series with the secondary and primary windings of one phase of the high frequency transformer 7 i. Upon realizing manipulation of the magnetic energy in the high frequency transformer by synchronously modulating the switches is an essential ingredient of this invention, the high frequency transformer is an essential component of any circuit topology of this invention and as a result, there are many other circuit topologies or circuit arrangements for this invention as long as the transformer is a critically essential component. The Push-Pull circuit topology 1 i toggles the switching between S1 and S2 (and likewise, between S3 and S4) for bi-symmetrical current flow through the windings, which is essential to avoid transformer saturation and the termination of transformer operation. Capacitors (C1, C2, C3, & C4) 6 i can be optionally added to supplement the junction capacitance of the switches in order to slow the rise time of the voltage or current during switching and for soft (i.e., resonant) switching. The Full Bridge circuit topology 2 i toggles the primary side switches (S1A, S1B, S2A, & S2B) or secondary switches (S3A, S3B, S4A, & S4B) 8 i in pairs (i.e., pair S1A and S2A closed with pair S1B and S2B opened or vice versa and likewise, pair S3A and S4A closed with pair S3B and S4B opened or vice versa) for bi-symmetrical current flow through the windings. Capacitors (C1A, C2A, C3A, C4A, C1B, C2B, C3B, & C4B) 9 i can be optionally added to supplement the junction capacitance of the switches (S1A, S2A, S3A, S4A, S1B, S2B, S3B, & S4B) 8 i in order to slow the rise time of the voltages or currents during switching or for resonant switching. For instance, slowing the rise and fall times of the switching edges will mitigate stress on the components, as well as allow compensation time for switch open and close delays while simultaneously allowing the switch junction voltage (or current) to pass through zero for soft opening or closing of the switches. There are many other possible arrangements of capacitors and inductors in the circuit to accomplish the same or for filtering. One characteristic that stands out with these circuits is the currents circulate (i.e. “circulating currents”) within the series circuit of switches, optional switch junction capacitors, and the high frequency transformer with very little high frequency escaping to the primary or secondary side ports. This can greatly decrease the size or need for filter devices, such as additional capacitors and inductors, on the primary or secondary sides to reduce stray harmonics propagated to the load or the power supply.

Transformers support two components of current, magnetizing current, which produces flux in the core of the transformer and the voltage across the port of the transformer, and load current, which produces no flux in the core due to the coupling action (i.e., mutual inductance) of the transformer. Magnetizing currents are designed to be substantially less than load currents. The term circulating currents used in this disclosure are magnetizing currents because when any set of switches on either side of the transformer is opened, the load current that originally flowed through the switch and complementary transformer phase winding ceases to exist in upon reaching steady state. To keep the flux in the transformer at steady-state, the change in load current(s) may be compensated by currents through the other switches (and phase windings); otherwise, only the transformer magnetizing current will flow, current will cease to exist, or the transformer will saturate and cease to exist. As a result, the judicial on-off timing (i.e., modulation-demodulation) of the switches (as will be discussed) uses this principle to transfer magnetic energy between the primary and secondary side of the transformer.

It should be understood that BMSCC (or RTEC) is the only technology that integrates a balanced phase winding Position Dependent Flux High Frequency Transformer (PDF-HFT) or PDF-HFT+PIF-HFT Combination as an integral component of its modulation control means of an electric machine or apparatus. The PDF-HFT or PDF-HFT-PIF-HFT transfers high power energy across the air gap with the potential of an automatic speed or position frequency component (i.e., self-commutation), although the PDF-HFT could be held at standstill too. In accordance with this unique architecture, BMSCC (or RTEC) incorporates two complementary components for modulation control of high frequency, high power transfer that differentiates BMSCC (or RTEC) from all other electric machine control. The first component is the “Initial Setup and Control of the Magnetizing Current”, which controls the PDF-HFT or PDF-HFT-PIF-HFT Combination flux (or air gap flux density) and port voltage in accordance with Faraday's Law. The second component, which occurs after the first component, is the “Power Transfer Control” component, which controls the actual transfer of high power across the air gap of the PDF-HFT or PDF-HFT-PIF-HFT Combination to the electric machine or electric apparatus being controlled by using an energy (or power) packet transfer method. Once steady-state is achieved in the PDF-HFT or PDF-HFT-PIF-HFT Combination by the first component (i.e., the Initial Setup and Control of the Magnetizing Current), the second component will replenish any power (or current) removed from one electrical port of the transformer by power (or current) entering the opposite port of the transformer (or visa-versa) to keep the oscillating magnetic field in air gap of the transformer at its steady-state condition. No other electric machine uses this two component control technique because no other electric machine controller uses a PDF-HFT (or PDF-HFT+PIF-HFT Combination) as described.

Unlike Pulse Width Modulation (PWM), Space Vector Modulation, Phase Modulation, or Frequency Modulation techniques for electric machine control, the high frequency modulation technology of BMSCC isolate the high frequency components within the PDF-HFT or PDF-HFT+PIF-HFT, which is designed for high frequency operation, and produce waveforms with virtually no harmonic content. As a result, BMSCC never subject the windings of the electric apparatus under control or the electrical power grid to high frequency content, which is detrimental to bearing and winding insulation life and cause high core and electrical loss.

Magnetizing Current Generator (MCG) Means: See Magnetizing Current Generator (MCG) block 24 of the Modulation Means Peculiar to BMSCC or RTEC 22 of the Primary Controller 6 & 19 and Secondary Controller 7 & 18 of FIG. 6. The “Initial Setup and Control of the Magnetizing Current Component” of the BMSCC is referred to as the Magnetizing Current Generator (MCG) means. The MCG establishes the steady-state oscillating magnetic field in the PDF-HFT (or PDF-HFT+PIF-HFT Combination) to satisfy the baseline design constraints of the PDF-HFT in accordance with Faraday's Law, such as the base-line frequency and air gap flux density for the operational design range of the PDF-HFT or PDF-HFT-PIF-HFT, by supplying an Magneto-Motive-Force (MMF) or Magnetizing Current in the winding set of the PDF-HFT or PDF-HFT-PIF-HFT. According to Faraday's Law, the Magnetizing Current is always 90 degrees lagging from the port voltage and contributes only imaginary power (or no real power) if electrical loss is neglected. The frequency of oscillation is significantly faster than the time base of the electric apparatus being driven, such as the PGM (i.e., 10 kHz versus 60 Hz). Without the setup of magnetizing current initially applied by the MCG at a frequency that is appropriate for the PDF-HFT or PDF-HFT-PIF-HFT design, any power transfer control technique would fail or the PDF-HFT would be inoperable because of potential of core saturation or heavy magnetizing current flow. Since the MCG shows imaginary power (disregarding loss), the MCG could be realized by a separate low power modulation means for driving an auxiliary low power winding set(s) solely for the setup of the air gap flux, or it could be integrated into any synchronous modem circuits or any switching algorithms for the second component (i.e., the “Power Transfer Control”). The MCG is the flux (or voltage) controller of BMSCC and has the ability to adjust the frequency of the oscillating magnetic field within the design constraints of the PDF-HFT or PDF-HFT+PIF-HFT Combination at any time for another level of control. An MCG can excite any phase winding in any combination and on any side of the PDF-HFT.

CTOM-CPDM Combination Means: See the CTOM or CPDM or CTOM-CPDM Combination Blocks 27 of Modulation Means Peculiar to BMSCC or RTEC 22 of the Primary Controller 6 & 19 and Secondary Controller 7 & 18 of FIG. 6. The “Power Transfer Control” component, which consists of new modulation control techniques for transferring high power energy across the air gap of the PDF-HFT or PDF-HFT+PIF-HFT Combination, are Compensated Transition Offset Modulation (CTOM), Compensated Pulse Density Modulation (CPDM), or any combination of CTOM or CPDM. The modulation techniques are considered “Compensated” because the gate timing of the Synchronous Modems is in “synchronous” time relationship to the unbiased positive and negative transitions or the symmetrical bipolar transitions (i.e., no low frequency bias) of the steady-state high frequency oscillating magnetic fields pre-established in the air gap (or the Magnetizing Currents in the windings) of the PDF-HFT or PDF-HFT+PIF-HFT Combination by the MCG. For instance, if the gate timing of the synchronous modem on one side of the PDF-HFT adds power (energy) to the oscillating magnetic field, the gate timing of the synchronous modem on the other side of the PDF-HFT must “compensate” for the additional energy in the oscillating magnetic field by removing the same amount of power (energy) from the oscillating magnetic field to preserve the steady-state condition of the oscillating magnetic field pre-established by the MCG.

As used herein, “compensated gating” refers to the act of gating or switching of the electrical power in synchronism to any measurable derivative of the high frequency oscillating magnetic field pre-established by the MCG, such as the voltage transitions or the cycles of the high frequency oscillating magnetic field.

As used herein, “compensated gating dynamics” refers to dynamically adjusting at any time the “compensated gating” by any half-cycle or by any time offset relative to a cycle reference, such as a cycle edge transition.

CTOM: See Compensated Transition Offset Timing Modulation (CTOM) block 25 of the Modulation Means Peculiar to BMSCC or RTEC 22 of the Primary Controller 6 & 19 and Secondary Controller 7 & 18 of FIG. 6. CTOM is a modulation means for conditioning electrical power that is peculiar to RTEC or BMSCC, which is transferring conditioned or re-fabricated high frequency power between the primary and secondary side of a Position Dependent Flux High Frequency Transformer (PDF-HFT) or PDF-HFT+PIF-HFT Combination with a steady-state oscillating magnetic field that is pre-established by a MCG means producing symmetrical bipolar carrier signals (i.e., no DC bias) and with synchronous modems on opposite sides for gating power packets in relation to the pre-established oscillating magnetic field. CTOM controls the relative time offset between the gating (i.e., negative-packet-on and positive-packet-on) of the synchronous modems on each side of the PDF-HFT or PDF-HFT+PIF-HFT Combination in synchronous relationship to the oscillating magnetic field established by the MCG. With proper high frequency filtering or strategic timing of the synchronous modem gating, virtually all the high frequency components, such as the carrier frequency, are confined to the PDF-HFT or PDF-HFT+PIF-HFT Combination, which is designed for high frequency operation, and as a result, leaving only the low frequency components at the terminals of the REG (or SEG).

-   -   As used herein, negative-packet-on and positive-packet-on define         terms that may require a complicated process of turning-on and         turning-off an array of power switches (i.e., power         semiconductors) in order to produce a positive or negative         transfer of power (or current) packets. For instance, there may         be a delay between turning-off one set of power switches before         turning-on another set of power switches to avoid any short         circuit potential.     -   As used herein, the switching energy of any burst of high         frequency electrical signals as a result of relative AC chopper         gate timing control is stored in the oscillating magnetic field         of the PDF-HFT (or PDF-HFT+PIF-HFT Combination) core and is         shareable between any Phase Winding assembled on the core of the         balance phase winding PDF-HFT (or PDF-HFT+PIF-HFT Combination).     -   As used herein, any discussion applying to the PDF-HFT equally         applies to the PDF-HFT+PIF-HFT Combination (or visa-versa).

FIG. 7 shows the progression of signals through the REG (or SEG) on the primary (stator) and secondary side (rotor) of the PDF-HFT (or PDF-HFT+PIF-HFT Combination) as a result of CTOM. Any discussion applying to the PDF-HFT equally applies to the PDF-HFT+PIF-HFT Combination (or visa-versa). For this disclosure, AC Chopper, chopper, chop, etc. are synonymous with synchronous modem or synchronous modem operation. The “Input Signal before AC Chopper” 1 a represents a single input signal to the electrical terminals on one side of the REG (or SEG), which may have many input signals. This signal could be an AC (i.e., sinusoidal) or DC waveform 5 a. The signal shown is actually a portion of a sinusoidal AC waveform with a zero crossing point 6 a through the zero voltage or current frame 7 a. In comparison, a DC waveform would be a constant level above or below the zero voltage or current frame 7 a with no zero crossing point 6 a. The “Primary Winding Signal after the Primary AC Chopper” 2 a, which results from gating the “Input Signal before Chopper” 1 a with the synchronous modem, drives its respective phase winding on one side of the PDF-HFT (i.e., the primary side). In this case, the Magnetizing Current Generator (MCG), which actually establishes the high frequency signal, is an integral component of the synchronous modem. The “Primary Winding Signal after the Primary AC Chopper” 2 a also depicts the magnetically induced signal on the secondary side of the PDF-HFT but with different modulation amplitude envelop 11 a, which is in accordance to the relative speed and position between opposing sides of the transformer and due to the transformer winding-turns ratio. In addition, the “Primary Winding Signal After the Primary AC Chopper” 2 a similarly represents the synchronism of the gate timing signals controlling the primary synchronous modem to the oscillating magnetic field pre-established by the MCG and for this case, the gating of the synchronous modems is congruent with the pre-established oscillating magnetic field, which could indicate that the MCG is built into the primary synchronous modem. In electrical reality, the straight edges seen in FIG. 7 may be rounder and slower. The “Primary Winding Signal after the Primary AC Chopper” 2 a has a negative going transition 8 a and a positive going transition 9 a per carrier cycle (or period) 12 a that symmetrically pass through the zero voltage or current 7 a at the chopping or carrier frequency. The chopping frequency is much higher than the frequency of the AC or DC waveform 5 a. The negative going transition 8 a and positive going transition 9 a per cycle (or period) similarly represents the negative-packet-on transition 8 a or positive-packet-on transition 9 a, respectively, of the AC chopper circuit (i.e., synchronous modem) while neglecting any time delays or other anomalies associated with the circuit.

The amplitude levels 11 a (dotted lines) represent the variation of the AC chopper signal waveform in accordance with the modulation amplitude envelope over time, which is the “Input Signal before AC Chopper” 5 a. By induction, the signal on the Secondary (or rotating) Winding of the PDF-HFT would be a similar signal as 2 a but with a different amplitude level 11 a due to the winding-turns ratio of the PDF-HFT, due to the amplitude levels 11 a on the primary side, or due to the degree of magnetic coupling as a result of the relative position between the stationary winding and the moving winding of the PDF-HFT. The degree of magnetic coupling, which is a function of relative speed (or mechanical frequency) and position between the stationary and moving windings of the PDF-HFT, would offset shift the waveform of the “Output Signal After AC Chopper” 23 a (after the secondary synchronous modem) according to the speed and position by changing the amplitude levels 11 a.

The “Gating Signal of the Secondary AC Chopper (A)” 3 a represents the negative-packet-on transition 13 a gating and positive-packet-on transition 14 a gating of the AC chopper circuit (i.e., synchronous modem) on the secondary (or moving) side of the PDF-HFT. The “Gating Signal (A) of the Secondary AC Chopper” 3 a is synchronized to the potentially dynamic cycle period 12 a of the “Primary Winding Signal after the AC Primary Chopper” 2 a for synchronous demodulation (or visa-versa).

CTOM is a modulation technique where the relative time offset between any positive 9 a (or 14 a) or negative 8 a (or 13 a) “bipolar” transitions of the carrier frequency on the “same” side of the PDF-HFT is adjusted in any dynamic combination for gating. Likewise, CTOM is a modulation technique where the relative time offset between any positive (between 14 a and 9 a) or negative (between 13 a or 8 a) bipolar transitions of the carrier frequency between “opposite” sides of the PDF-HFT is adjusted in any dynamic combination for gating. CTOM would vary the relative gate timing between transitions 8 a (or 13 a) and 9 a (or 14 a) with respect to the period 12 a including in combination with the changing period of 12 a as managed by the Magnetic Current Generator (MCG). During any dynamic transition change, the cycle period 12 a between the synchronous modems on each side of the PDF-HFT is synchronized regardless of timing dynamics of the transitions including the timing transitions between cycles. Said differently, CTOM is time adjusting the gating in any combination between transitions on Primary Winding Signal After Primary AC Chopper 2 a or in any combination between transitions on the Gating Signal (A or B) on The Secondary Chopper 3 a, 4 a or in any combination between the Primary Winding Signal After Primary AC Chopper 2 a transitions and the Gating Signal (A, B) of The Secondary Chopper 3 a, 4 a transitions. Further, the combinational time offset adjustments could be fixed or dynamically changed during any cycle or during any other cycle, which is managed by the MCG. Controlling the combinational adjustments is the result of gating the “negative-packet-on transition” or “positive-packet-on transition” of the synchronous modems at virtually the same time the adjustments are desired. The offset shift between transitions could be referenced or controlled on the rotor (or moving) side, the stator side, or both sides as long as the cycle periods 12 a between the two sides are synchronized, which means the cycle period 12 a of the synchronous modems on either side of the PDF-HFT (or PDF-HFT+PIF-HFT Combination) must acclimate (i.e., phase lock) to the same period even with a dynamic change in cycle period by the MCG. The primary and secondary sides are timing symmetrical and either side can be the initiator or the controller of the timing dynamics. The timing dynamics could be referenced or controlled on the rotor (i.e., secondary) side, the stator (i.e., primary) side, or both sides as long as the two sides are synchronized.

As an example, the “Gating Signal (A) of the Secondary AC Chopper” 3 a could include a positive shift 15 a in gate timing as a result of CTOM or a negative shift 24 a as shown in the “Gating Signal (B) of the Secondary AC Chopper” 4 a, which would average (i.e., control) the power weighting (or sampling) between primary and secondary synchronous modems. For instance, the Power transfer direction through the synchronous modem, which is represented by a current vector with direction passing through a resistor 26 a and 27 a, would occur several times over the period 12 a of the carrier signal and as a result, would variably average the combined power levels depending on the degree of offset shift. Shifting the “Gating Signal (A) of The Secondary AC Chopper” 3 a odd multiples of 180 degrees (or half cycles) relative to the “Primary Winding Signal After Primary AC Chopper” signal 2 a would result in an inverted (or negative) signal of the “Output Signal After AC Chopper” 23 a. This is crudely represented by the dotted AC or DC output waveform 20 a, which corresponding to the dotted waveform of the “Gating Signal (B) of The Secondary AC Chopper” signal 4 a. Likewise, the solid AC or DC output waveform 20 a of the “Output Signal After AC Chopper” 23 a corresponds to the solid waveform of the “Gating Signal (A) of The Secondary AC Chopper” signal 3 a, which is shifted 180 degrees (or half cycle) from the Gating Signal (B) of The Secondary AC Chopper” signal 4 a. Similarly, shifting the “Gating Signal (A) of The Secondary AC Chopper” 3 a even multiples of 180 degrees (or zero degrees) or half cycles relative to the “Primary Winding Signal After Primary AC Chopper” signal 2 a would result in a non-inverted (or positive) “Output Signal After AC Chopper” 23 a (solid waveform). Shifting the “Gating Signal (A) of The Secondary AC Chopper” 3 a odd multiples of 90 degrees (or quarter cycles) relative to the “Primary Winding Signal After Primary AC Chopper” signal 2 a (as is shown) would result in no voltage or current because resulting oscillating power has no average power. It should now be understood that varying the offset shift other than 90 or 270 degrees would vary the voltage or current transfer amplitude and the polarity of the transfer. Overall, the result (with proper filtering) is the solid (or dotted) AC or DC output Waveform 20 a as shown in the “Output Signal after AC Chopper” 23 a. It should also be understood that the “Output Signal after the AC Chopper” 23 a would also include any mechanical shift or frequency (speed) between the rotor and stator winding sets of the PDF-HFT.

In keeping with the spirit of the preceding example, the positive or negative gating shift per high frequency chopper period could vary in accordance to the desired waveform (or the contrived or re-fabricated waveform) that is relative to the waveform of the Input Signal before AC Chopper 1 a. Under this situation, the magnetic core energy would be shared between phases in order to produce or re-fabricate the desired phase waveform envelop by CTOM, since the input of a particular phase waveform being control (“Input Signal Before AC Chopper” 1 a) may have no amplitude while the desired output waveform (“Output Signal After AC Chopper” 23 a) may require a finite amplitude. In addition, the time offset between transitions would vary in a timely fashion according to the amplitude of the desired waveform. Under this method of CTOM control the torque angle (or the power factor) could potentially be adjusted by sharing the magnetic energy in the core of the PDF-HFT as a result of CTOM gating. Again, the mechanical speed would be an additional component in the resulting output waveform 23 a. The shift 22 a represents the offset shift of the output waveform 23 a in relation to the input waveform 1 a as a result of the mechanical speed/position between the stationary and moving winding sets of the PDF-HFT or as a result of modulating the gate timing shift (15 a, 24 a) by CTOM in accordance to the desired (or contrived) waveform.

Understanding that Modulation is the beating of signals, a simple trigonometry analysis will show how power can be controlled by CTOM. Let Cos (Wt) represent the gate transition timing of the synchronous modem on one side of the PDF-HFT and Cos (Wt+φ) represent the gate transition timing of the synchronous modem on other side of the PDF-HFT. Both transition timings are out of phase by φ but operate at the same frequency, W, and are therefore, synchronized. Further, the resulting high frequency carrier signal (i.e., power signal) has a low frequency modulation envelope, Cos (W₆₀t) due to the AC phase signal (i.e., 60 Hz for this example). Using simple trigonometry, the following results from beating Cos (Wt) with Cos (Wt+φ) and again with Cos (W₆₀t):

${{\cos \left( {W_{60}t} \right)} \cdot \left\{ {{{Cos}({Wt})} \cdot {{Cos}\left( {{Wt} + \phi} \right)}} \right\}} = {{{{Cos}\left( {W_{60}t} \right)} \cdot \left\{ {{{Cos}({Wt})} \cdot \left\lbrack {{{{Cos}({Wt})} \cdot {{Cos}(\phi)}} - {{{Sin}({Wt})} \cdot {{Sin}(\phi)}}} \right\rbrack} \right\}} = {{{{Cos}\left( {W_{60}t} \right)} \cdot \left\{ \left\lbrack {{{{Cos}({Wt})} \cdot {{Cos}({Wt})} \cdot {{Cos}(\phi)}} - {{{Cos}({Wt})} \cdot {{Sin}({Wt})} \cdot {{Sin}(\phi)}}} \right\rbrack \right\}} = {{{{Cos}\left( {W_{60}t} \right)} \cdot \left\{ {\frac{1}{2} \cdot \left\lbrack {{{Cos}(\phi)} + {{{Cos}\left( {2{Wt}} \right)} \cdot {{Cos}(\phi)}} - {{{Sin}\left( {2{Wt}} \right)} \cdot {{Sin}(\phi)}}} \right\rbrack} \right\}} = {{{Cos}\left( {W_{60}t} \right)} \cdot \left\{ {\frac{1}{2} \cdot \left\lbrack {{{Cos}(\phi)} - {{Cos}\left( {{2{Wt}} + \phi} \right)}} \right\rbrack} \right\}}}}}$

At 0 or 180 degrees for φ, the power signal is

${{Cos}\left( {W_{60}t} \right)} \cdot \left\{ {\frac{1}{2} \cdot \left\lbrack {1 - {{Cos}\left( {2{Wt}} \right)}} \right\rbrack} \right\}$

or

${{- {{Cos}\left( {W_{60}t} \right)}} \cdot \left\{ {\frac{1}{2} \cdot \left\lbrack {1 - {{Cos}\left( {2{Wt}} \right)}} \right\rbrack} \right\}},$

respectively, which have average power levels.

At 90 or 270 degrees for φ, the power signal is

${{Cos}\left( {W_{60}t} \right)} \cdot \left\{ {\frac{1}{2} \cdot {{Sin}\left( {2{Wt}} \right)}} \right\}$

or

${{- {{Cos}\left( {W_{60}t} \right)}} \cdot \left\{ {\frac{1}{2} \cdot {{Sin}\left( {2{Wt}} \right)}} \right\}},$

respectively, which are sinusoidal, and accordingly, have no average power or have zero power level.

-   -   NOTE: By changing the offset timing of the gating between the         synchronous modems on each side of the PDF-HFT, φ, the         propagation of power can be varied. Since any fast transition         periodic signal, such as a square wave, can be represented as a         series (i.e., Fourier Series) of sinusoids with harmonics of the         fundamental frequency, an AC chopped signal, such as the AC         chopped signal resulting from gating the synchronous modems,         would be represented by a Fourier series of Cos (W_(N)t) or Cos         (W_(N)t+φ), where N represents frequency harmonic terms, and the         combinational results would be similar to the simple analysis,         which used Cos (Wt) with Cos (Wt+φ), although their would be N         like terms.

CPDM: See Compensated Pulse Density Modulation (CPDM) block 26 of the Modulation Means Peculiar to BMSCC or RTEC 22 of the Primary Controller 6 & 19 and Secondary Controller 7 & 18 of FIG. 6. CPDM is a modulation means for conditioning electrical power that is peculiar to RTEC or BMSCC, which is transferring conditioned or re-fabricated high frequency power between the primary and secondary side of a Position Dependent Flux High Frequency Transformer (PDF-HFT) or PDF-HFT+PIF-HFT Combination with a steady-state oscillating magnetic field that is pre-established by a MCG means producing symmetrical bipolar carrier signals (i.e., no DC bias) and with synchronous modems on opposite sides for gating power packets in relation to the pre-established oscillating magnetic field. CPDM controls and synchronizes the number of contiguous gating transitions of the synchronous modems during a burst (or string) of high frequency cycles that occur at specific time intervals (or frames). Each frame occurs multiple times during the period of the low frequency waveform of the modulation envelope. The number of cycles per string is weighted according to the desired shape and magnitude of the modulation envelope waveform desired to be transferred between the synchronized AC power switches of the synchronous modems on each side of the PDF-HFT. The weighting (or density of the string) and the frame time interval can be dynamically adjusted at anytime. With proper high frequency filtering or strategic timing of the synchronous modem gating, virtually all the high frequency components, such as the carrier frequency, are confined to the PDF-HFT, which is designed for high frequency operation, leaving only the low frequency components at the terminals of the PDF-HFT.

To generate a string of cycles during a given interval, the synchronous modems on the primary side of the PDF-HFT would be continuously gated in synchronism to the carrier frequency to achieve the desire number of cycle density (or weight) for that string during a given frame. Likewise, the synchronous modem on the secondary side of the PDF-HFT, which is synchronized to the synchronous modem on the primary side, would be gated during the same frame; thereby, demodulating the high frequency carrier and showing only the desired electrical weight of the string, which is the combined weight or polarity (i.e. accumulation) of all the half-cycle energy directed into one polarity by the synchronous demodulation. Shifting the gating of the synchronous modem on only one side of the PDF-HFT by one-half cycle (or 180 degrees) would effectively negate (or invert) the weighting. As a result, other affects could be achieved by half cycle shifting the gating between the synchronized AC choppers on each side of the PDF-HFT during any frame. For instance, half cycle shifting the gating on one side of the PDF-HFT by an incremental number during any frame interval of weight cycles would retrieve smaller portions of the power density of the string, since a portion of the string would not be gated or synchronously demodulated. This portion of energy could be absorbed by another AC Phase if the AC choppers of that particular AC phase, which continues to gate (or synchronously demodulate) during the same frame interval. The weighting and cycle shifting could be referenced or controlled on the rotor side, the stator side, or both sides as long as the two sides are synchronized to the oscillating magnetic field pre-established by the MCG.

FIG. 8 shows the progression of signals through the REG (or SEG) on the primary (stator) and secondary side (rotor) of the PDF-HFT (or PDF-HFT+PIF-HFT Combination) as a result of CPDM. Any discussion applying to the PDF-HFT equally applies to the PDF-HFT+PIF-HFT Combination (or visa-versa). For this disclosure, AC Chopper, Chopper, etc., similarly represent a synchronous modem or synchronous modem operation. The “Input Signal before AC Chopper” 1 b is the input signal to the REG (or SEG). This signal could be an “AC or DC Supply Waveform” 5 b. The signal shown is actually a portion of a sinusoidal waveform with a voltage or current crossing point 4 b through the “Zero Voltage or Current of AC or DC Supply” baseline 6 b. A DC waveform would be a constant level above or below the zero voltage or current baseline 6 b with no zero crossing point 4 b. The “Primary Winding Signal after the AC Chopper” 2 b, which results from gating the Input Signal 1 b with a synchronous modem and similarly represents the gate timing signals controlling the synchronous modem, drives its respective phase winding on the primary side of the PDF-HFT. In this case, the Magnetizing Current Generator (MCG), which actually establishes the high frequency signal, is an integral component of the synchronous modem. The “Primary Winding Signal after the AC Chopper” 2 b also represents the magnetically induced secondary winding signal of the PDF-HFT. In electrical reality, the straight edges depicted are generally rounder and slower. Each string length 12 b and 13 b of cycles 7 b of gated negative-packet 8 b and positive-packet 9 b on-transitions is weighted with a different number of cycles 7 b according to the voltage or current level desired for that particular frame 14 b with a resolution of weighting down to half cycles. In this case, string 12 b contains 2.5 cycles and string 13 b contain 4.5 cycles. The beginning of each string of cycles would be separated by a frame 14 b that could be a time interval based on an arbitrary or fixed number of cycles or a dynamically changing number of cycles. The interval of a frame consists of a weighted number of cycles that should be equal to or larger than the maximum anticipated weight of any string. The amplitude level 5 b of the “Input Signal before AC Chopper” 1 b is included on the amplitude of the “Primary Winding Signal after the AC Chopper” 2 b, which is shown by the dotted amplitude levels 11 b. The overlapping timing of the “Gating Signals of the Secondary AC Choppers” 3 b synchronously demodulates the secondary winding signals to produce an “Output Signal after AC Chopper” 4 b. The “AC or DC output waveform” 15 b will have a zero crossing point 14 b that may be phase shifted 17 b according to the desired (i.e., contrived or re-fabricated) waveform as a result of the CPDM weighting sequences and the mechanical speed or position of the moving winding set of the PDF-HFT in relation to the stationary winding set of the PDF-HFT.

For one example, assume the following sequential weighting per string in ten sequential frames is 1, 5, 7, 5, 1, −1, −5, −7, −5, and −1 with the frame interval occurring every fixed 50 cycles of timing and with no relative movement between the PDF-HFT windings. The weighting of each string would be referenced to the frame weight of 50 or 1/50, 5/50, 7/50, 5/50, 1/50, − 1/50, − 5/50, − 7/50, − 5/50, and − 1/50. Further, assume the “Input Signal before AC Chopper” 1 b is a DC waveform. The sequential frames represent the digitized weighting closely resembling a low amplitude sinusoidal waveform or analog waveform, which has a maximum amplitude weight of 5/50 or 1/10. The “Primary Winding Signal after the AC Chopper” 2 b represents the same weighting sequence of cycles and frames on both sides of the PDF-HFT (or PDF-HFT+PIF-HFT Combination) due to inductive coupling. Assuming the same gating occurs for “Gating Signals of the Secondary AC Choppers” 3 b, the demodulated result would be similar to the “Output Signal After AC Chopper” 4 b that is a sinusoidal waveform with the combined discrete energy packets based on the weighting sequence just describe. With any means of filtering the combined discrete packets represented by the cross-hatched area 22 b (while referencing only string 20 b) would be smoothed out to a waveform represented by the dotted or solid AC or DC output waveform 15 b as referenced to the zero voltage axes 16 b. Any movement of the PDF-HFT or any waveform of the “Input Signal before AC Chopper” 1 b, other than DC, would be included.

Swapping the positive-packet-on-transition timing 9 b and the negative-packet-on-transition timing 8 b (i.e., positive-packet-on-transition would be 8 b and negative-packet-on-transition would be 9 b) of the “Gating Signals of the Secondary AC Choppers” 3 b by a half-cycle or 180 degree offset shift in relation to the “Primary Winding Signal After the AC Chopper” 2 b, the polarity of the “AC or DC waveform” 5 b in relation to the “Zero Voltage or Current” 6 b would be inverted as shown by the dotted envelop 15 b of the “Output Signal After AC Chopper” 4 b. FIG. 8 attempts to show an instance of shifting the secondary string signal 21 b relative to the primary string signal 20 b by a positive shift 19 b of one-half cycle or 180 degrees with the hatched area 22 b showing the result of the demodulation. Without the half-cycle offset shift of the carrier signal, the solid envelope 15 b shown for the “Output Signal after AC Chopper” 4 b would result. The primary side 2 b and secondary side 3 b strings can be relatively shifted 19 b by any number of positive or negative half cycles during any Frame. Odd half-cycle shifts result in a combined inverted (or negative) weight and even half cycle shifts result in a combined non-inverter (or positive) weight. The cross-hatched area 22 b attempts to show how the weight is applied to the signal.

Gating may be initiated on the primary side, the secondary side, or any combination. CTOM and CPDM Combination: See CTOM and CPDM Combination block 27 of the Modulation Means Peculiar to BMSCC or RTEC 22 of the Primary Controller 6 & 19 and Secondary Controller 7 & 18 of FIG. 6. Compensated Time Offset Modulation (CTOM) and Compensated Pulse Density Modulation (CPDM) operate by the timely gating of the synchronous modems in synchronous relation to the negative and positive transition of the oscillating magnetic field on the PDF-HFT or PDF-HFT+PIF-HFT Combination, which is pre-established by the MCG. Essentially, CTOM or CPDM opens discrete windows on a timely basis for sharing the magnetic energy of the PDF-HFT or PDF-HFT+PIF-HFT Combination (i.e., High Frequency Magnetic Energy Sharing or HFMES). It should be obvious to experts that CTOM and CPDM can be supported in any combination.

CPDM, CTOM, or CPDM-CTOM Combination may require filtering components, such as capacitors, on both terminal sides (or low frequency sides) of the REG (or SEG) to bypass any high frequency components that are the results of CPDM and CTOM techniques, such as when the transition timing of the choppers on each side of the PDF-HFT do not exactly overlap. Because of the high frequency of the carrier signals, any filtering component would be of low impedance. In essence, the high frequency components are confined to the PDF-HFT or PDF-HFT+PIF-HFT Combination and isolated from the low frequency electric apparatus.

CPDM, CTOM, or CPDM-CTOM Combination may synchronize the high frequency carrier of each phase in accordance to a single phase AC system or to a multiphase AC system. For instance, the synchronous timing of the high frequency carrier signals for all AC-Phases may coincide or the synchronous timing of the high frequency carrier signals for each AC-Phase may be without coincidence, such as by a phase offset time in accordance with the desired high frequency multiphase system (i.e., the synchronous timing of the high frequency carrier for each AC phase of a 3-phase AC system will be 120 degrees offset in likeness to the modulation envelopes of the 3-Phase AC system).

High Frequency Magnetic Energy Sharing (HFMES) Art: See High Frequency Magnetic Energy Sharing (HFMES) block 28 of the Modulation Means Peculiar to BMSCC or RTEC 22 of the Primary Controller 6 & 19 and Secondary Controller 7 & 18 of FIG. 6. The high frequency carrier signals from all the winding phases store the switching energy in the magnetic field of the PDF-HFT (or PDF-HFT-HRCRT Combination). This high frequency oscillating magnetic energy (i.e., power) can be shared between all phase windings of the PDF-HFT in any proportion as the result of CTOM or CPDM individually controlling (modulating) the current (or power) through the balanced phase windings. CTOM controls power by transition edge timing and CPDM controls power by digitally weighting the number of half cycles per frame. As a result of CTOM or CPDM, only a portion of the energy in the high frequency magnetic field would be allocated to any one phase as previously discussed with the remaining portion of energy available for allocation (or sharing) between the other phases as desired. High Frequency Magnetic Energy Sharing (or HFMES) as was just discussed is different from inherently re-distributing or changing the high frequency magnetic flux by changing the magnetic path as a result of movement. It should be understood that HFMES is specific to the high frequency magnetic energy in the PDF-HFT (or PDF-HFT-HRCRT Combination) and mutually exclusive from the low frequency magnetic energy of any electric apparatus being controlled.

The following analysis demonstrates how CPDM or CTOM share magnetic energy between phases, which is referred to as High Frequency Magnetic Flux Energy Sharing (or HFMES). FIG. 9 gives the vector representation of the “low frequency” modulation envelopes of the three phase (i.e., 3-Phase) “excitation” signals on each side of the REG (or SEG) in an x-y coordinate reference system. PDF-HFT is interchangeable with PDF-HFT+PIF-HFT Combination in this analysis. Likewise, REG is interchangeable with SEG in this analysis. More appropriately, these signals could also be the vector representation of a snap-shot of the low frequency modulation envelope amplitude by the high frequency carrier signals on any side of the PDF-HFT in the x-y coordinate reference. The signals are referred to as representation or reference signals only for explanatory purposes. The signals are the actual AC phase voltages, AC phase currents, or oscillating magnetic energy as a result of the multiphase excitation. The three phase legs of the Reference 3-Phase Signal are Leg_1 1 c, Leg_2 2 c and Leg_3 3 c, respectively, could be considered the stator winding excitation signals of the PDF-HFT by the stator synchronous modems. The three phase legs of the Resulting 3-Phase Signal are Leg_1′ 4 c, Leg_2′ 5 c and Leg_3′ 6 c, respectively, could be considered the signals from rotor winding terminals of the PDF-HFT. Since it is a three phase representation, each leg of each AC phase is separated by 120 degrees or 2π/3 radians 7 c. Similarly, a six phase representation would have a 60 degree or π/3 radians of separation between phase legs. The signals for each 3-Phase system rotate together at an angular frequency determined by the given AC excitation frequency (i.e., 60·2π Radians per second@60 Hz). Not included in this figure, the rotation could include a mechanical rotation, which is possible with the PDF-HFT. The low frequency and phase of the reference (or stator) 3-Phase signals are W_(x)t+φ_(x) 8 c. The desired frequency and phase of the resulting (or rotor) 3-Phase signals are W_(y)t+φ_(y) 9 c. The difference between the reference and resulting signals is [(W_(x)t+φ_(x))±(W_(y)t+φ_(y))] 10 c. The energy stored in the magnetic field is the difference between the energy leaving the PDF-HFT (i.e., leaving on the Resulting 3-Phase Signals) and the energy entering the PDF-HFT (i.e., entering on the Reference 3-Phase Signals). Assuming the signals are balanced, the entire analysis will be a simple analysis of a single leg, Leg_1′. The sum of the components of the each reference signal phase that are right angle 11 c intersections to the phase leg of observation is the desired resulting signals. The dotted Reference 12 c is the negative extrapolation of Leg_1′, which determines the resulting component attributed to Leg_3 of the reference vector.

The reference signals represented by the set of 3-Phase vectors pass through a bi-directional modulator circuit, which are the synchronous modems of the REG. By modulating and then demodulating the signals by the modulation art specific to Real Time Emulation Control (or Brushless Multiphase Self-Commutation Control), which is CTOM or CPDM or combination, the synchronous modem circuit of the REG functions as a variable window into sharing the high frequency magnetic energy of any of the reference signals of the figure, which are actually the conditioned phase excitation signals of the REG. Automatically included in each signal are amplitude components associated with the step-up, step-down, or neutral winding-turns ratio between the stator and rotor winding sets (transformer ratio) of the PDF-HFT and the amplitude components associated with the mechanical speed and phase component according to the relative movement between the rotor and stator winding sets of the PDF-HFT.

The following gives a simple analysis of changing the frequency, W_(x), and phase, φ_(x), of the input multiphase signal to a different frequency, W_(y), or phase, φ_(y), which considers the PDF-HFT to be stationary (such as at a potential standstill condition) and as a result, does not include any mechanical speed and phase component of a moving PDF-HFT. The symmetry of the REG synchronous modem circuits allow electronic modulation or demodulation to occur on either side of the PDF-HFT of the REG.

By simple vector arithmetic and assuming the normalized amplitudes, each leg of the three phases will be:

Leg_1 = Sin(W_(x)t + ϕ_(x 1)); ${{{Leg\_}2} = {{Sin}\left( {{W_{x}t} + \phi_{x\; 2} + \frac{2\pi}{3}} \right)}};$ ${{{Leg\_}3} = {{Sin}\left( {{W_{x}t} + \phi_{x\; 3} + \frac{4\pi}{3}} \right)}};$

Where:

-   -   W_(x) Electrical Frequency;     -   φ_(x1), φ_(x2), φ_(x3) Angle of Electrical Frequency for each         phase with the difference between phase 1, 2, & 3 depicting         balanced or unbalanced phases.

The Modulations on each phase are:

-   -   Modulation for Leg_1:

A Cos((W_(x)+W_(y))t+φ_(x)±φ_(y1));

-   -   Modulation for Leg_2:

${A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 2}} + \frac{2\pi}{3}} \right)}};$

-   -   Modulation for Leg_3:

${A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 3}} + \frac{4\; \pi}{3}} \right)}};$

-   -   Where:         -   W_(y) Electrical High Frequency of the desired waveform;         -   φ_(y1), φ_(y2), φ_(y3) Angle of Electrical Frequency of the             desired waveform for each phase with the difference between             phase 1, 2, & 3 depicts balanced or unbalanced phases;         -   A the adjustable (i.e., by modulation or magnetic             amplification) normalized amplitude (or multiplier), which             can be a multiplier value between 0 and A′, where A′ is the             winding-turns ratio of the PDF-HFT;         -   ± Direction of frequency (clockwise or counter-clockwise             rotation on polar coordinates).

Let ±(W_(y)t+φ_(y)) be the frequency and phase of the desired waveform with the (±) indicating the direction (clockwise or counter-clockwise).

As the transition (such as a square wave) become faster (straighter), the relation is a Fourier series of harmonic components, which is a duplication of the proceeding relations for each term in the Fourier series.

Then considering only balanced phases (i.e., φ_(x1)=φ_(x2)=φ_(x3)) for simplicity:

Leg_1′:

${{{Leg\_}1^{\prime}} = {{A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 1}}} \right)} \times {{Sin}\left( {{W_{x}t} + \phi_{x}} \right)}} + {A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 2}} + \frac{2\; \pi}{3}} \right)} \times {{Sin}\left( {{W_{x}t} + \phi_{x} + \frac{2\; \pi}{3}} \right)}} + {A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 3}} + \frac{4\; \pi}{3}} \right)} \times {{Sin}\left( {{W_{x}t} + \phi_{x} + \frac{4\; \pi}{3}} \right)}}}};$

Leg_1′ relation can be further expanded:

${{Leg\_}1^{\prime}} = {{A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 1}}} \right)} \times {{Sin}\left( {{W_{x}t} + \phi_{x}} \right)}} + {{A\;\begin{bmatrix} {{{{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 2}}} \right)}{{Cos}\left( \frac{2\; \pi}{3} \right)}} -} \\ {{Sin}\left( {{\left( {{W_{x}t} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 2}}} \right){{Sin}\left( \frac{2\; \pi}{3} \right)}} \end{bmatrix}} \times {\quad{\left\lbrack {{{{Sin}\left( {{W_{x}t} + \phi_{x}} \right)}{{Cos}\left( \frac{2\; \pi}{3} \right)}} + {{{Cos}\left( {{W_{x}t} + \phi_{x}} \right)}{{Sin}\left( \frac{2\; \pi}{3} \right)}}} \right\rbrack + {{A\;\begin{bmatrix} {{{{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 3}}} \right)}{{Cos}\left( \frac{4\; \pi}{3} \right)}} -} \\ {{Sin}\left( {{\left( {{W_{x}t} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 3}}} \right){{Sin}\left( \frac{4\; \pi}{3} \right)}} \end{bmatrix}} \times {\quad{\left\lbrack {{{{Sin}\left( {{W_{x}t} + \phi_{x}} \right)}{{Cos}\left( \frac{4\; \pi}{3} \right)}} + {{{Cos}\left( {{W_{x}t} + \phi_{x}} \right)}{{Sin}\left( \frac{4\; \pi}{3} \right)}}} \right\rbrack;}}}}}}}$

To simplify term expansion for a more obvious solution, consider a two phase system:

${{{Leg\_}1^{\prime}} = {{A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 1}}} \right)} \times {{Sin}\left( {{W_{x}t} + \phi_{x}} \right)}} + {A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 2}} + \frac{\pi}{2}} \right)} \times {{Sin}\left( {{W_{x}t} + \phi_{x} + \frac{\pi}{2}} \right)}}}};$   Or: ${{Leg\_}1^{\prime}} = {{A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 1}}} \right)} \times {{Sin}\left( {{W_{x}t} + \phi_{x}} \right)}} + {{A\;\begin{bmatrix} {{{{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 2}}} \right)}{{Cos}\left( \frac{\pi}{2} \right)}} -} \\ {{Sin}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 2}}} \right){{Sin}\left( \frac{\pi}{2} \right)}} \end{bmatrix}} \times {\quad{\left\lbrack {{{{Sin}\left( {{W_{x}t} + \phi_{x}} \right)}{{Cos}\left( \frac{\pi}{2} \right)}} + {{{Cos}\left( {{W_{x}t} + \phi_{x}} \right)}{{Sin}\left( \frac{\pi}{2} \right)}}} \right\rbrack;\mspace{20mu} {{{Or}\text{:}{Leg\_}1^{\prime}} = {{A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 1}}} \right)} \times {{Sin}\left( {{W_{x}t} + \phi_{x}} \right)}} - {A\; {{Sin}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 2}}} \right)} \times {{Cos}\left( {{W_{x}t} + \phi_{x}} \right)}}}};}}}}$

-   -   By letting (φ_(y1)=−φ_(y2)=φ_(y)) or driving with inverted         choppers, one solution is:

Leg_(—)1′=A Cos((W _(x) +W _(y))t+φ _(x)±φ_(y)−(W _(x) t+φ_(x)));

-   -   And for simplicity, if (φ_(y)=0) and (φ_(x)=0), then Leg_1′         becomes:

Leg_(—)1′=A Cos(±W _(y) t);

-   -   This fixed result is purely a “real” component.     -   By letting (φ_(y1)=φ_(y2)=φ_(y)) or driving with non-inverted         choppers, another solution is:

Leg_(—)1′=A Cos((W _(x) ±W _(y))t+φ _(x)±φ_(y)+(W _(x) t+φ _(x)));

-   -   And for simplicity, if (φ_(y)=0) and (φ_(x)=0), then Leg_1′         becomes:

Leg_(—)1′=A Cos((2W _(x) ±W _(y))t);

-   -   This oscillating result is purely an “imaginary” component.

These same solutions hold for two or more phases.

Leg_2^(′): ${{Leg\_}2^{\prime}} = {{A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 1}} - \frac{2\; \pi}{3}} \right)} \times {{Sin}\left( {{W_{x}t} + \phi_{x}} \right)}} + {A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + \phi_{x} + \phi_{y\; 2}} \right)} \times {{Sin}\left( {{W_{x}t} + \phi_{x} + \frac{2\; \pi}{3}} \right)}} + {A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 3}} + \frac{2\; \pi}{3}} \right)} \times {{Sin}\left( {{W_{x}t} + \phi_{x} + \frac{4\; \pi}{3}} \right)}}}$

-   -   By letting (φ_(y1)=−φ_(y2)=φ_(y)) or driving with inverted         choppers, one solution is:

${{{Leg\_}2^{\prime}} = {A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y}} - {\left( {{W_{x}t} + \phi_{x}} \right)\frac{2\; \pi}{3}}} \right)}}};$

-   -   And for simplicity, if (φ_(y)=0) and (φ_(x)=0), then Leg_2′         becomes:

${{{Leg\_}2^{\prime}} = {A\; {{Cos}\left( {{{\pm W_{y}}t} + \frac{2\; \pi}{3}} \right)}}};$

-   -   By letting (φ_(y1)=φ_(y2)=φ_(y)) or driving with non-inverted         choppers, another solution is:

${{{Leg\_}2^{\prime}} = {A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y}} + \left( {{W_{x}t} + \phi_{x}} \right) + \frac{2\; \pi}{3}} \right)}}};$

-   -   And for simplicity, if (φ_(y)=0) and (φ_(x)=0), then Leg_2′         becomes:

${{{Leg\_}2^{\prime}} = {A\; {{Cos}\left( {\left( {{2W_{x}} \pm W_{y}} \right)t\frac{2\; \pi}{3}} \right)}}};$ Leg_3^(′): ${{Leg\_}3^{\prime}} = {{A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y\; 1}} - \frac{2\; \pi}{3}} \right)} \times {{Sin}\left( {{W_{x}t} + \phi_{x}} \right)}} + {A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + \phi_{x} + \phi_{y\; 2} - \frac{2\; \pi}{3}} \right)} \times {{Sin}\left( {{W_{x}t} + \phi_{x} + \frac{2\; \pi}{3}} \right)}} + {A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + \phi_{x} + \phi_{y\; 3}} \right)} \times {{Sin}\left( {{W_{x}t} + \phi_{x} + \frac{4\; \pi}{3}} \right)}}}$

-   -   By letting (φ_(y1)=−φ_(y2)=φ_(y)) or driving with inverted         choppers, one solution is:

${{{Leg\_}3^{\prime}} = {A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y}} - \left( {{W_{x}t} + \phi_{x}} \right) + \frac{4\; \pi}{3}} \right)}}};$

-   -   And for simplicity, if (φ_(y)=0) and (φ_(x)=0), then Leg_3′         becomes:

${{{Leg\_}3^{\prime}} = {A\; {{Cos}\left( {{{\pm W_{y}}t} + \frac{4\; \pi}{3}} \right)}}};$

-   -   By letting (φ_(y1)=φ_(y2)=φ_(y)) or driving with non-inverted         choppers, another solution is:

${{{Leg\_}3^{\prime}} = {A\; {{Cos}\left( {{\left( {W_{x} \pm W_{y}} \right)t} + {\phi_{x} \pm \phi_{y}} - \left( {{W_{x}t} + \phi_{x}} \right) + \frac{4\; \pi}{3}} \right)}}};$

-   -   And for simplicity, if (φ_(y)=0) and (φ_(x)=0), then Leg_3′         becomes:

${{{Leg\_}3^{\prime}} = {A\; {{Cos}\left( {{\left( {{2W_{x}} \pm W_{y}} \right)t} + \frac{4\; \pi}{3}} \right)}}};$

These solutions do not include the mechanical phase and speed component, which is attributed to the relative mechanical relationship between the rotor and stator winding nor the amplification component due to the winding-turns ratio.

In conclusion, with the proper modulation parameters, the signal Sin(W_(x)t+φ_(x)) can be electronically re-fabricated to A Sin(W_(y)t+φ_(y)) by frequency, phase, or waveform shape, regardless of any movement or position of the PDF-HFT shaft. More importantly, the propagation of power through the REG (or SEG) can be re-fabricated from one waveform to another waveform by sharing the high frequency oscillating magnetic energy through any combination of the CTOM or CPDM techniques of BMSCC (or RTEC) while remaining in any time or speed variant reference frame. Further, once the parameters for the desired waveform are established, the Phase-Lock-Loop (PLL) mechanism or the electromagnetic self-commutation of the PDF-HFT holds these parameters regardless of speed (i.e., even zero speed) or until new waveform parameters are desired and entered.

It should be understood that “Waveform Re-fabrication” is using the MCG and any CTOM-CPDM combination to directly share the “high frequency magnetic energy” existing between balanced phase windings in the core of the PDF-HFT or PDF-HFT+PIF-HFT Combination while transferring power to the electric apparatus under control. The modulation carrier gating (switching) is in synchronous relationship to the oscillating high frequency magnetic energy. The high frequency magnetic energy is energy in the core of the PDF-HFT that oscillates at the same frequency as the modulation gating. In contrast, “Frequency Synthesis”, which uses derivatives of Pulse Width Modulation, Phase Modulation, or Space Vector Modulation, shares the “low frequency electromagnetic energy” in the core of the actual electric machine entity under control and in the storage components of the modulator circuit (such as the DC Link Stage) for transferring power to the electric machine under control. The low frequency electromagnetic energy is effectively constant energy in relation to the high frequency modulation switching (or gating).

Note: As used herein, adjustment, re-fabrication, and conditioning of the signal waveforms are similar terms to describe the conversion operation on a waveform.

Environmental Stress Immunity (ESIM) Art: See Environmental Stress Immunity Means (ESIM) 30 of Synergistic Art peculiar to BMSCC or RTEC 23 of the Primary Controller 6 & 19 and Secondary Controller 7 & 18 of FIG. 6. Since the shafts of the Brushless Multiphase Self-Commutation Controller (BMSCC) and the electric apparatus under the control of BMSCC, such as the PGM, must be attached to convey operating speed and position, BMSCC and the controlled electric apparatus are closely coupled. As a result, BMSCC is the (only) electric machine control art that compels the environmentally sensitive control and power electronic components and the electrical components to be subjected to the same operating (or environmental) conditions as the electric apparatus under control, such as heat, mechanical stress, etc. In contrast, all other control technologies, such as FOC, impose no restriction on mounting the sensitive electronic and electrical equipment remotely from the operating conditions subjected on the electric machine under control. Electronic components are active components, such as integrated circuits, power semiconductors, etc. Electrical components are passive components, which include all other components, such as capacitors, inductors, printed circuit boards, the PDF-HFT, the PIF-HFT, moving and stationary body winding sets, etc. Years of proprietary research, development, and prototyping by this inventor, which cannot be obvious to electric machine experts or engineers because there is no prior BMSCC art, made it apparent that incorporating environmental immunity means against heat, humidity, altitude, mechanical stress, etc. is crucial to the practicality of BMSCC because of the integral proximity of BMSCC to the electric machine being controlled and to the same environmental conditions. It follows that any art that mitigates the environmental stress on the REG, the SEG, or the PGM is new and useful improvement for BMSCC and is considered new synergistic invention for BMSCC.

Heat is transferred (or dissipates) by convection (i.e., carried away from the heat source by a moving fluid, or gas, etc.), conduction (i.e., molecular agitation and energy absorption through a medium), vaporization (i.e., changing from one state to another), or radiation (i.e., electromagnetic waves or light). It follows that any of the heat transfer methods can be passive or active. A passive transfer of heat, such as using a copper bar to conduct the heat away from an electronic circuit, uses no separate power source to move the heat away from the heat source. An active transfer of heat, such as a motorized fan to blow cool air over an electronic circuit or an acoustic means to move heat by waves, uses a separate power source to move the heat away from the heat source. Active transfer means rely on acoustics, fans, pumps, thermocouples, etc., and a cooling medium, such as cooling fluids, cooling gases, cooling mists, etc.

Environmental stress immunity means specific to Brushless Multiphase Self-Commutation Control (or Real Time Emulation Control) comprise at least the following:

-   -   New art specific to RTEC (or BMSCC) means and systems is         incorporating any electronic and electrical components with the         composition, design, construction, or manufacture that allows         reliable operation above 49 degrees Celsius, which is the         minimum operating temperature of the insulation of the windings         of any electric apparatus complemented with BMSCC (or RTEC).         This includes exotic electronic components, such as components         based on silicon carbide, gallium arsenide, etc.     -   New art specific to RTEC (or BMSCC) means and systems is         incorporating any potting or mounting of the electronic and         electrical components to protect the electronic and electrical         components from mechanical stress, such as shaft acceleration,         or to improve heat dissipation.     -   New art specific to RTEC (or BMSCC) means and systems is         incorporating any passive or active form of heat immunity, such         as (but not limited to) the use of ultrasound (such as that use         in a humidifier) to mist a fluid, such as oil, water,         antifreeze, etc., for a cooling medium or to propagate heat         acoustically, etc., or an active means, such as a fan, pump, or         vacuum, to move the cooling medium across the heat sensitive         components, or thermocouples, or other heat conduction means,         such as using the actual winding conductor material to dissipate         heat, or heat pipes.     -   New art specific to RTEC (or BMSCC) means and systems is         incorporating slots, channels, sections, or seams into the rotor         or stator lamination stacks of the electric machine core for the         flow of cooling medium. The slots, channels, sections, or seams         could be integrated with vanes, propellers, or means to force         the flow of cooling medium with the movement of the rotor.

CTOM-CPDM Modulation Start-Up Art: CTOM-CPDM Modulation Start-up Art is an integral component of CTOM-CPMDM Modulation peculiar to BMSCC. The CTOM-CPDM Modulation Startup follows. First, establish the “Initial Setup and Control of the Magnetizing Current” in the PDF-HFT (or PDF-HFT+PIF-HFT Combination) by the MCG in accordance with the port voltages and the baseline design frequency of the PDF-HFT (or PDF-HFT+PIF-HFT Combination). If the MCG is integrated into the synchronous modems, it is conceivable that only synchronous modems (with an integrated MCG means) on one side of the PDF-HFT (or PDF-HFT+PIF-HFT Combination) will be started, since parametric information has yet to be established for satisfactory calculation of CTOM or CPDM modulation control. Further, this pre-established oscillating magnetic field may be the only means to supply power to any control logic on the other side of the PDF-HFT (or combination). Second, begin the Basic Three Step Process Control Means (BTPCM) of RTEC (or BMSCC) that includes the gating of the synchronous modems on both sides of the transformer after the parametric information has been captured and calculated, which effectively establishes the “Power Transfer Control” by CTOM, CPDM or combination.

Basic Control Process (BTPCM) Art: See the Basic Three Step Process Control Means (BTPCM) Art 31 that is Synergistic Art Peculiar to BMSCC or RTEC 23 of the Primary Controller 6 & 19 and Secondary Controller 7 & 18 of FIG. 6. Real Time Emulation Control (RTEC) or Brushless Multiphase Self-Commutation Control (BMSCC) requires a simple three basic step control process, which is unlike the complex four basic step control process of derivatives of FOC that must include its distinguishing electromagnetic process disruption by an offline or dissimilar process consisting of formulating reference signals, processing of formed signals or reference signals Of with multiphase “speed-variant” to “speed-invariant” transformations (i.e., sometimes called reference rotation) of the reference signals, and finally, frequency synthesizing the excitation.

The Basic Three Step Process Control Means (BTPCM) follows. For Process Control Step One, measure the voltage, the current, the speed, the position, the torque, or a combination of any derivative thereof as seen at the electrical and mechanical terminals of the electric machine, which may be acquired locally such as directly from the port of the machine or may be acquired remotely, such as at the electrical distribution facility. For Process Control Step Two, with the acquired data determine a response to achieve the desired or expected electrical or mechanical parameters, including power factor, torque, or speed. Methods employed to determine the response may be by calculations, such as mathematical, logical, lookup, or comparative, or by communications. For Process Control Step Three, adjust or re-fabricate the shape of the “excitation” waveform of the “modulation envelop” to achieve the desired results by the modulation techniques of CTOM or CPDM that are peculiar to RTEC (or BMSCC), which includes magnetic energy sharing. Other parameters determined by either measurement or calculation for more complex control would still be a derivative of the basic three step process. Understand that BTPCM is for optimizing the performance of the electric machine being controlled (i.e., the PGM) and to control the distinguishing feature of RTEC (or BMSCC), which is inherent self commutation with any input frequency of excitation that will continually accelerate the PGM without the Basic Three Step Control measures.

It should be understood that the manual three step process does not include formulation of reference signals and the manual time (or speed) variant to time (or speed) invariant transformation process (i.e., reference rotation) on the reference signals associated or required with other means of control. Therefore, the Basic Three Step Process Control Means is basic and may comprise other sub-steps but not the manual time variant to time invariant transformation process.

Simultaneous Mechanical Control Process (SMAC) Art: See Simultaneous Mechanical Adjustment Control (SMAC) 29 of the Modulation Means Peculiar to BMSCC or RTEC 22 of the Primary Controller 6 & 19 and Secondary Controller 7 & 18 of FIG. 6. Another control method, which is peculiar to RTEC or BMSCC, is the ability to mechanically move the relative position (i.e., phase angle) between the stationary body of the REG (or SEG) and a stationary reference, such as the PGM stationary body, while simultaneously operating under RTEC or BMSCC. Simultaneous Mechanical Adjustment Control (or SMAC), while simultaneously operating under RTEC or BMSCC, allows adjustment of parameters, such as the Power Factor (PF), of any electric machine controlled by RTEC or BMSCC, while operating with a given torque or voltage level. This manual adjustment technique could be automatic by incorporating other means, such as an electromechanical servo system that mechanically adjusts the phase angle automatically or on command. Another art for SMAC is to pre-adjust the PF (such as unity PF) or Torque Angle at the origin of manufacture or site for a specific or default base torque, current, voltage, or power level of the electric machine.

Capture, Control, Command, and Communication Processor (CCCC) Art: See Capture, Control, Command, and Communication Processor (CCCC) 33 of Synergistic Art Peculiar to BMSCC or RTEC 23 of the Primary Controller 6 & 19 and Secondary Controller 7 & 18 of FIG. 6. Although the PDF-HFT (or PDF-HFT+PIF-HFT Combination) naturally performs the intensive electromagnetic processing in real time by inherent means (i.e., Real Time Emulation Control or Brushless Multiphase Self-Commutation Control), less intensive processing operations, such as Capture, Control, Command, and Communication (or CCCC) processing, among other derivatives of CCCC processing, are still required for satisfactory operation of RTEC or BMSCC. Capture could be measuring the signal conditions, such as the synchronous timing between the synchronous modems, which is a unique requirement of RTEC or BMSCC, or the voltages and current levels. Control could be algorithms, calculations, or adjustments, such as “adjusting” the modulation (or gating) of the synchronous modems to meet a “calculated” parameter requirement determined from a captured measurement. Command could be user desired entry, such as “set speed to” from a keyboard. Communication could be relaying any information from the moving body to the stationary body or retrieving a command from a user friendly interface, such as a remote keyboard. As a result, any combination of Digital or Analog Electronic Processors may be placed on the secondary side (see Secondary Controller 7 of FIG. 6), the primary side (see the Primary Controller 6 of FIG. 6), or either side for performing CCCC operations. The digital or analog electronic processing could be soft programmed, such as by an arrangement of stored electronic instructions, hard-programmed, such as any wired arrangement of amplifiers, digital switching gates, integrated circuits, etc., or soft-wired, such as with Field Programmable Devices. Obviously, the intensity of the desired CCCC operations dictates the processing power required and is a natural requirement for any electric machine controller but in direct contrast to any derivative of FOC, the CCCC operations of BMSCC (or RTEC) do not include any comparably intensive processing operations, such as speed variant to speed invariant transformations and frequency synthesis.

Speed Position Resolver (SPRM) Art: See Speed/Position Resolver Means (SPRM) 34 of Synergistic Art Peculiar to BMSCC or RTEC 23 of the Primary Controller 6 & 19 and Secondary Controller 7 & 18 of FIG. 6. The PDF-HFT changes the output waveform to a speed-synchronized waveform naturally and without delay in accordance to the relative speed and position between the rotor and stator winding sets because the PDF-HFT is basically a Multiphase Electromagnetic Self-Commutator or Multiphase Electromagnetic Computer. Therefore, the speed and absolute position of the shaft can be determined by incorporating any means to compare any primary to any secondary waveform (or visa versa) of the PDF-HFT or the output of the REG or SEG. As a result, the PDF-HFT, the REG system, or the SEG system is an inherent speed-position resolver means or transducer (SPRM), which is an important parameter for the Basic Three Step Process Control Means (BTPCM) of RTEC (or BMSCC).

Synchronizing Means (SM): See Synchronizing Means (SM) 32 block of the Synergistic Art Peculiar to BMSCC or RTEC 23 of the Primary Controller 6 & 19 and Secondary Controller 7 & 18 of FIG. 6. Brushless Multiphase Self-Commutation Control (BMSCC) or Real Time Emulation Control (RTEC) and in particular, the modulation techniques of CTOM, CPDM, or combination thereof stipulate the synchronous modems on each side of the air gap of the PDF-HFT (or PDF-HFT+PIF-HFT Combination) be synchronized to the carrier frequency, which is pre-established by the Magnetic Current Generator (MCG). RTEC (or BMSCC) Synchronizing Means (SM) use either a Wireless Communication Means (WCM), such as using an optical or Radio Frequency (RF) medium (with antenna), Circular Transformer means for a pure communication data medium (perhaps without an RF modulation), or a Phase Lock Loop (PLL) means to establish the synchronizing clock, which all power gating is referenced. For instance, a PLL (on either side of the rotor or stator side or on both sides) means containing circuitry or software control that would monitor the difference between transitions of the carrier power signal by means of a phase detector, produces a synchronized reference frequency that coincides with the PDF-HFT (or PDF-HFT+PIF-HFT Combination) oscillating magnetic field. In another for instance, the communication means broadcasts a synchronizing framing signal or information packet that allows the CCCC means to re-synchronize.

The synchronous means coincides with a measurable derivative of the high frequency oscillating magnetic field pre-established in the air gap of the PDF-HFT or PDF-HFT+PIF-HFT Combination by the MCG.

As used herein, a “measurable derivative” refers to any signal, which is a result of the oscillating magnetic field that gives a similar reference signal waveform of the oscillating magnetic field and can be measured by means of a sensor. This includes voltages across the phase winding, currents in the phase windings, etc., which can also relate to signal transitions, signal half-cycles, and signal cycles.

Wireless Communication Means (WCM): See Wireless Communication Means (WCM) block 20 of the Synergistic Art Peculiar to BMSCC or RTEC 23 of the Primary Controller 6 & 19 and Secondary Controller 7 & 18 of FIG. 6. A Wireless Communication Means (WCM) could propagate parametric information, logic power, or synchronization means between both sides of the PDF-HFT or PDF-HFT+PIF-HFT Combination. It should be obvious that many circuit and software means can implement the WCM. For instance, the PDF-HFT, the PIF-HFT, or the combination may include another winding set on the primary and secondary side of the transformer with a mutual air gap area that most likely does not dynamically change with movement that are specifically for a wireless means of propagating logic power or a low level signal for communication.

Soft Switching Compensation (SSC) Means: See Soft Switching Compensation Means (SCC) block 35 the Synergistic Art Peculiar to BMSCC or RTEC 23 of the Primary Controller 6 & 19 and Secondary Controller 7 & 18 of FIG. 6. CTOM, CPDM or combination thereof are established by the timely synchronous gating of the negative-packet-on-transition and positive-packet-on-transition of the bi-directional power switches (i.e., gates) of the synchronous modems, which would best occur at the zero level crossing of the current or voltage of the high frequency carrier signal. Gating the negative and position transitions at the zero level (or crossing) of the voltage or current is referred to as soft switching (or resonant switching) because it minimizes electrical stress on electrical and electronic components since the switching occurs at the lowest power level. Further, Soft Switching (i.e., Resonant Switching) improves the efficiency and switching speed of the circuit because it effectively utilizes the intrinsic impedance of the electrical circuit to its advantage. For another example, ceasing the flow of current through a switch component in series with other reactive components, such as inductors, by opening the switch at a determined current level will lower voltage overshoot, which is directly proportional to the time derivative of the current flow change, and as a result, minimize overall component stress and ratings.

The zero crossing of voltage or current “inherently” occurs in BMSCC (or RTEC) because the power signals must be unbiased (i.e., bipolar transitions without DC bias, which is termed bi-symmetric transitions in this document) for efficient electrical power propagation across the air gap of the PDF-HFT by high frequency induction. However, electronic switches (i.e., power semiconductors) of a power circuit together with the gate driving circuit show a finite delay time between the turn-on and turn-off command action and the actual turn-on or turn-off of the switch. Further, delay times change with temperature and circuit component anomalies and as a result, the actual turn-on and turn-off are not entirely deterministic at a given time or for a given circuit condition. Unfortunately, any deviation from the exact switch turn-on or turn-off at the zero crossing shows the negative effects of hard switching, which is the indiscriminate turn-on or turn-off switching while disregarding the potentially high level of current or voltage across the gate of the power switch at the time of the switching.

BMSCC (or RTEC) may use any means to soft switch as near to the exact zero crossings as possible by compensating for indeterminate delays. One circuit means averages out delay times over repeated measurement iterations of gate turn-on (and turn-off) actions. As used herein, this method will be referred to as Iterative Averaging. The circuit measures the “time period”, t₁, between the start of the “gate transition command” time, which is the time the control circuit commands a turn-on or turn-off action to occur, and the power “switch transition sense” or when the resulting transition of the power semiconductor or power signal is actually sensed (by a sensing circuit) to have occurred. The sense circuit can detect a “before zero crossing” or an “after zero crossing” and may detect any parameter that gives the level of switching energy to determine the proximity to the zero crossing. If the actual power switch turn-on (or turn-off) transition occurs before (or after) the “inherent” zero crossing of the steady-state oscillation, a faster transition through the zero crossing than the expected steady state dv/dt of the inherent signal transition (or hard switch) will occur, which can be measured. The “level” of the switch transition sense determines the proximity of the actual switched transition to the inherent zero crossing and the “polarity” of the switch transition sense determines on which side of the zero crossing the transition occurred. Both level and polarity can be measured, which gives an indication of how far from the expected zero crossing and on what side of the expected zero crossing did the actual power switching occur. This “time period”, t₁, will be adjusted (according to the level detected) and added or subtracted (according to the polarity detected) from the next gate transition command. The next iteration measures the “time period”, t₂, between the start of the “gate transition command” and the “switch transition sense” and accordingly adds or subtracts the next “time period”, t₂, from the previous transition gating time, t₁. Over time, intrinsic component time, t_(N), any delays associated with sense circuit delays, temperature, and other circuit anomalies are average out and will be constantly readjusted as dynamic changes take place. It should be understood that “level” is a relative term, referring to power, voltage, current, etc.

Assume a 10 kHz inherently oscillating excitation is occurring in the BMSCC. As a result, a positive-on-transition will occur every 100 microseconds and the power switching clock (synchronizing clock, S_(clock)) would tick every 100 microseconds (the negative-on-transition has been neglected for simplicity but compensation follows the same analogy). As an example, assume t₁ was measured to be 1 microsecond from the time the “on-gate transition command” was issued and the actual power switch turned-on is sensed, “switch transition sense”. Further, the power switched (or turned-on) after the inherent signal zero crossing as indicated by the “polarity” of the switched transition sense. The next “on-gate transition command” should occur 1 microsecond before the expected time to command an actual turn-on of the power switch at the zero crossing of the inherent oscillating signal, which is (S_(clock)−t₁). At the next gate turn-on command, t₂ was measured to be 0.1 microsecond and the polarity was measured to be before the inherent signal zero crossing. Therefore, the next on-gate command would occur 0.9 microseconds before the expected time to command an actual turn-on of the power switch, which is (S_(clock)−t₁+t₂). This process goes on infinitum or until the modulation gating is terminated.

The sensing for the actual switch on and off transitions will occur well within a half-cycle period of the carrier signal or within the next transition time (100/2 microsecond for this example). If no finite voltage or current transition is sensed within this period, the “time period” will be zero (and could be discarded), since it is assume, the actual power semiconductor transition occurred very close, if not coincidentally, to the zero crossing of the expected carrier signal transition. It should be understood, that this prediction algorithm or Soft Switching Compensation (SSC) is peculiar to the new art of RTEC (or BMSCC) and the modulation techniques of BMSCC, which is MCG with any combination of CTOM or CPDM.

Any Electric Machines Art: See Any Singly-Fed or Doubly-Fed Electric Machine System with BMSCC or RTEC 36 of FIG. 6. By employing either SEG or REG means, any doubly-fed or singly-fed electric machine can be controlled by BMSCC, including Asynchronous, Synchronous, or Reluctance electric machines. Further, any configuration can be supported such as linear form-factor, rotating form-factor, axial flux form-factor, radial flux form-factor, or transverse flux form-factor. The phase windings from one side of the BMSCC (i.e., the secondary side) would connect phase-to-phase to the phase windings of the electric machine being controlled, while the other side of the BMSCC (i.e., the primary side) would connect phase-to-phase to the phase legs of the electrical power grid. The BMSCC can be used to excite the multiphase wound-rotor active winding set (i.e., rotor active winding set) of a Wound-Rotor Doubly-Fed Electric Machine with the REG configuration. In the Wound-Rotor Doubly-Fed Electric Machine configuration, the BMSCC can be connected in parallel, which is the classical method, or in series with the phase windings of the PGM for an advanced brushless wound-rotor synchronous doubly-fed electric machine system. In addition, another BMSCC with the SEG configuration may simultaneously excite the stationary multiphase active winding set (i.e., stator active winding set) of a Wound-Rotor Doubly-Fed Electric Machine. With the SEG configuration, the BMSCC can be used to excite the stationary multiphase active winding set (i.e., stator active winding set) of any singly-fed electric machine, if the singly-fed electric machine places the passive winding set or the permanent magnet assembly on the rotor, such as the classical squirrel cage induction machine, or with the REG configuration, the BMSCC can be used to excite the rotor multiphase active winding set, if the singly-fed electric machine places the passive winding set or the permanent magnet assembly on the stator. Similarly, using the most advanced techniques for the PGM entity 1 of FIG. 6, the most state-of-art electric machine that includes BMSCC is realized. For instance, an electric machine that uses BMSCC, where the moving windings are embedded in a cylindrical or disk of thin composite material for low inertia, would be another essence of this invention. The BMSCC controlled electric machine can be put in a modular pancake configuration (i.e., axial flux) and multiple pancake configurations can be stacked along a common axle for incremental power increases, while perhaps leaving a space between each module for cooling means. Because BMSCC means is unknown to electric machine experts or engineers, any electric machine that uses BMSCC means, which may include up-to-date or new science design, construction, winding form-factor or manufacture techniques, becomes new art or invention to any Singly-Fed or Doubly-Fed Electric Machine System with BMSCC or RTEC 36 of FIG. 6, which could include exotic bearings, such as magnetic bearings, air bearing, etc., or any combination of efficient or exotic materials, such as low loss magnetic materials from nanotechnology or amorphous metals, ribbons, powdered metals, laminations, etc., or efficient or exotic low loss conduction materials. The exceptional and symmetric control of BMSCC could more easily support or complement magnetic levitation or bearings.

Superconductor Electric Machines Art: See Any Singly-Fed or Doubly-Fed Electric Machine System with BMSCC or RTEC 36 of FIG. 6. Superconductor Electric Machines are synchronous electric machines with a superconductor field-winding (or wound-field). The superconductor field-winding is a DC electromagnet (i.e., wound-field) that can achieve extremely high air gap Flux Density or extremely high magnetizing currents (or MMF) without resulting electrical loss. Superconductor Electric Machines have numerous daunting problems, which are easily solved with RTEC (or BMSCC). Presently, Superconductor Electric machines must incorporate conventional electronic control, such as FOC, for practical operation. Due to the modulation techniques placed on the active winding set by conventional electronic control, frequency harmonics are imposed on the superconductor field-winding that quench the magnetic field and greatly compromise the superconductor. Further, the superconductor field-winding must be placed on the rotor, which greatly complicates the logistics of the cryogenic fluid support of the superconductor field-winding. RTEC (or BMSCC) does not intentionally drive the active winding set with high frequency modulation, which greatly reduces harmonics and superconductor quenching, and BMSCC “brushlessly” relocates the multiphase active winding set to the rotor side while simultaneously relocating the superconducting field-winding to the stator side for simplified logistical support of the field-winding cryogenics.

It should be understood, that a superconductor winding is basically a DC electromagnet or field winding and the superconductor electric machine is considered a field wound synchronous electric machine. Replacing the field winding of any field wound synchronous electric machine with a permanent magnet realizes a permanent magnet synchronous machine, which is a viable configuration for the BMSCC as discussed for the superconductor electric machine.

Magnetic Bearing Art: Because of the extraordinary control offered by BMSCC and its ability to adjust air gap magnetic fluxes of the PGM entity via a phase-lock-loop approach, magnetic bearings can be easily realized.

Rotary or Stationary Phase or Frequency Converter Invention: Traditionally, a Rotary Phase Converter is an electric machine that converts an alternating current (AC) electrical signal from one phase to another phase (i.e., from single phase AC to three phase AC) as its principle purpose. Similarly, a Rotary Frequency Converter is an electric machine that converts an electrical signal from one frequency to another frequency (i.e., DC to 5 Hz). Rotation of the Rotary Converter precipitates the phase or frequency conversion. Electro-mechanical conversion may occur but is not a principle result of a Rotary Converter. Rotation could be forced by an external electric machine driving the shaft or could use the intrinsic torque of the Rotary Converter, itself. The traditional Rotary Converter consists of a conventional electric machine, such as an induction (or asynchronous) electric machine or a synchronous electric machine with complementary components.

The BMSCC (or RTEC) is a compact, lightweight, efficient Stationary or Rotary Frequency or Phase Converter because of its high frequency of operation. See Stationary or Rotary Phase or Frequency Converter block 39 of the BMSCC Dependent Inventions 44 of FIG. 6.

The Rotary or Stationary Frequency Converter follows the Synchronous Speed Relation.

${fm} = \frac{{\pm {fs}} \pm {fr}}{P}$

The frequency of the waveform at the primary terminals of the BMSCC can be converted to another frequency at the secondary terminals by sharing the energy of the oscillating magnetic field in the core of the PDF-HFT by any combination of CPDM or CTOM, fr, or by rotating (or moving) the shaft, fm, in accordance with the Synchronous Speed Relation. While adjusting only, fm, the BMSCC is a Rotary Frequency Converter because the conversion is done with rotation. In addition, any contrived rotation could also be a means to drive a cooling fan to actively dissipate heat from the system. While adjusting only, fr, the BMSCC is a Stationary Frequency Converter because the conversion is done with frequency re-fabrication by sharing the magnetic energy between phase windings with no need for rotation.

Likewise, the BMSCC (or RTEC) is a Stationary or Rotary Phase Converter. The BMSCC can convert a given number of phases on the primary side to another number of phases on the secondary side, while satisfying the Synchronous Speed Relation even at standstill by sharing the energy of the oscillating magnetic field in the core of the PDF-HFT by any combination of CPDM or CTOM, as was discussed.

For instance, supplying the Reference Phase windings (Leg_1 1 c. Leg_2 2 c and Leg_3 3 c) of FIG. 9 with the proper polarity of DC, Leg_1 1 c, Leg_2 2 c and Leg_3 3 c would be stationary vectors in time space or fs=0 (see Synchronous Speed Relation). If the rotation speed, fm, was 5 Hz, the Resulting Phase Winding Signals (Leg_1′ 4 c, Leg_2′ 5 c and Leg_3′ 6 c) would be 3-Phase, 5 Hz AC. The result is a Rotary Phase Converter, which converts a single phase waveform (i.e., DC in this case) to a 3-Phase AC waveform, and a Rotary Frequency Converter, which converted DC to 5 Hz AC. Similarly, if the rotation speed fm=0 (or no rotation), and the frequency, fs, and phase of Leg_1 1 c, Leg_2 2 c and Leg_3 3 c was electronically converted to a 3 Phase 5 Hz waveform by sharing the high frequency oscillating magnetic energy in the PDF-HFT by any combination of CTOM or CPDM, the Resulting Phase Winding Signals (Leg_1′ 4 c, Leg_2′ 5 c and Leg_3′ 6 c) would be 3-Phase, 5 Hz AC. In both cases, the Resulting Phase Winding Signals would be additionally modified with the frequency or phase of any difference of movement of the shaft. With these two examples presented, applying any mechanical speed or phase to the shaft, fm, or supplying any electrical frequency or phase, fr or fs, by sharing the high frequency oscillating magnetic energy of the PDF-HFT between winding sets by any combination of CTOM or CPDM would fabricate the results to virtually any waveforms. Further, this example demonstrates each of three phase windings being fed with DC (or Single Phase AC) with the correct polarity; however, other phase winding arrangements with the correct winding-turns ratio and combinational CTOM-CPDM conditioning as calculated by trigonometry may be a simpler alternative depending on the overall design circumstances. The example shows the DC input is electronically re-fabricated to 5 Hz by any combination of CTOM and CPDM, which is a reasonable slip frequency for Induction Electric Machine operation. Of course, any slip frequency could have been produced. According to the Synchronous Speed Relation, 5 Hz slip frequency (and phase) is locked regardless of any change in speed of the shaft. While this describes an example of re-fabricating DC to 5 Hz AC, it will be understood that the frequency can be other than 5 Hz.

Incorporating a Stationary (or Static) Excitation Generator (or SEG), the Rotary BMSCC Phase or Frequency Converter transfers the conversion from stationary-side to stationary-side (or visa-versa) without brushes or slip-rings or to another speed that is different than the movement speed of the SEG shaft. Incorporating a Rotor Excitation Generator (or REG), the BMSCC Phase or Frequency Converter transfers the conversion from stationary-side to moving-side (or visa-versa). Incorporating either a REG or SEG while locking the shaft from movement, the BMSCC transfers the conversion from stationary-side to stationary-side (or visa-versa) with no speed or position component induced on the waveform; therefore, the frequency or phase waveform conversion would be strictly the result of sharing the energy in the high frequency oscillating magnetic field by any combination of CTOM or CPDM.

With a supplemental means of storage, such as a flywheel, a battery, a super-capacitor, another electric machine entity, or another electric machine with high inertia, etc., the stationary or rotary phase or frequency converter based on BMSCC is an Uninterruptible Power Supply (UPS).

With the example, it should now be evident that the REG or SEG with the new art of BMSCC can control any type (i.e., Asynchronous, Synchronous, or Reluctance) or category (i.e., Singly-Fed or Doubly-Fed) of electric machine with electromagnetic self-commutation and with power sources of any number of AC-Phases (including DC) or any frequency. The conversion example just discussed, which converts single phase DC to 5 Hz 3-Phase AC is an example of a BMSCC controller driving the stationary active winding set of an off-the-shelf Induction (or Asynchronous) Electric Machine, where the shafts of the BMSCC and the Induction Electric Machine are attached and move at the same speed to phase-locked the slip frequency to one example frequency of 5 Hz, regardless of the speed of the shafts. Essentially, this is an example of “True” Self-Commutated DC Electric Machine, although the actual electric machine entity is an induction electric machine.

Pole-Pair Emulator Invention: Because the REG (or SEG) with BMSCC (or RTEC) is a rotary frequency converter means, any electric machine mated with BMSCC can emulate an electric machine with a given number of pole-pairs. As shown by the synchronous speed relation, the speed of the shaft of the electric machine is dependent on the frequency of excitation and the number of magnetic pole pairs distributed about its air gap area. By rotating (or moving) the shaft of the REG (or SEG) proportionally to the rotating (or moving) shaft of the PGM (or the electric machine to be controlled), the fractional number of magnetic-poles emulated would be in accordance to the proportional speed ratio between the REG (or SEG) shaft and the PGM shaft. As an example, if a means was incorporated, such as a transmission of gears, chains, or belts or separately with another adjustable speed motor, Synchro-Pair (or Servo-Pairs), or changing ratio transmission combination for moving the speed of the PDF-HFT rotating (or moving) body at a contrived speed, which is twice the speed as the body of the PGM for this example, the speed range of the PGM would be reduced by one-half or would appear to operate like an electric machine with twice as many magnetic pole-pairs. The more common method would attach the PGM and REG bodies (or shafts) directly to rotate at the same speed, which would be a magnetic pole-pair emulation of one-to-one.

It should now be evident that Pole-Pair Emulation can be any fractional or integral ratios, including a variable ratio by rotating (or moving) the shaft at an adjustable speed by any means, such as an adjustable speed drive (or another electric machine driving the REG or SEG shaft) or Synchro-Pair. Since a Synchro-Pair is a rotary (or moving) electrical transformer that forces the same movement applied to any shaft of any Synchro of the pair onto the other Synchro of the pair, the REG or SEG as the Pole-Pair Emulator could be mounted remotely from the electric apparatus under BMSCC control with variable pole-pair emulation.

With pole-pair emulation, the synchronous speed relation becomes:

${fm} = \frac{{\pm {fs}} \pm {fr}}{P \star \frac{V_{HFRT}}{V_{PGM}}}$

Synchronous Speed Relation (With Pole-Pair Emulation);

Where:

-   -   fs is the electrical frequency of the AC excitation on the         stator (or primary) winding set (i.e., 60 Hz) and is related to         the speed of the magnetic field in the air-gap;     -   fr is the electrical frequency of the AC excitation on the rotor         (or moving) (or secondary) winding set, which is virtually zero         for Singly-Fed or Permanent Magnet Electric Machines;     -   fm is the mechanical speed (revolutions per second) of the         rotor;     -   P is the number of magnetic “pole-pairs”;     -   V_(PDF-HFT) Is the velocity of the PDF-HFT in relation to the         velocity of the PGM (V_(PGM));     -   V_(PGM) is the velocity of the PGM in relation to the velocity         of the PDF-HFT (V_(PDF-HFT));

VSCF Wind and Renewable Energy Invention: See Variable Speed Constant Frequency (VSCF) Wind (or Any Prime Mover) Turbine block 37 of the BMSCC Dependent Inventions 44 of FIG. 6. Although Electric Machines perform their choirs virtually unnoticed, Electric Machines are the backbone of the electricity infrastructure and are virtually everywhere. Electric Machines will generate electricity for distribution only when mechanically driven by a fixed or variable speed prime mover, which has always been defined as an energy source, such as wind, tidal, wave, steam, fuel, engine, motor, etc. Similarly, Electric Machines will produce mechanical power when excited with electricity. Without supplying electricity or mechanical power, electric machines have no applicable purpose.

As used herein, prime mover is used in the classic sense, which is an initial agent that puts a machine in motion. It is considered the energy source. A prime mover needs a mechanical converter, such as an electric motor, a propeller, an engine, etc., to put the prime mover, such as electricity, wind, hydraulics (i.e., tidal, wave, etc.) fossil fuels, etc., to work

RTEC or BMSCC contributes new art to all applications requiring an electric machine driven by fixed or variable speed prime movers to generate electricity. Several applications are particularly receptive to BMSCC considering today's renewed sensitivity to energy. One such application is converting the energy from a variable speed windmill (or wind turbine) to the fixed frequency AC electrical utility by BMSCC, which does not incorporate any derivative of Field Oriented Control (FOC) or field-windings. This same application can be equally applied to any prime mover, such as wind energy, wave energy, tidal energy, etc.

Wind, Tidal, and Wave energy are prime movers that are variable in nature. These prime movers can power an electric generator that supplies electricity to a fixed frequency electric distribution system. This makes a Variable Speed Constant Frequency (VSCF) Electric Machine with Brushless Multiphase Self-Commutation Control (BMSCC) or Real Time Emulation Control (RTEC) an attractive alternative for generating electricity from renewable prime movers; in particular, from wind (using wind turbines).

All wind turbines (i.e., windmills) are composed of multiple components. The major components are the tower, the turbine or propeller blades, the propeller wind capture control and motor mechanism for pitch, yawl, braking, etc., the transmission to convert the low speed propeller shaft to a high speed most compatible with the electric machine generator, and the electric machine for converting the variable mechanical power from the prime mover to fixed frequency electricity. Variable Speed Constant Frequency (VSCF) wind conversion is the best means for converting wind energy to electrical energy, because it imposes the least stress on the mechanical components and it captures wind energy over a broader range of wind variation.

A VSCF Electric Machine with Brushless Multiphase Self-Commutation Control (BMSCC) or Real Time Emulation Control (RTEC) offers a leap in performance and benefits over present technology, such as derivatives of Flux Oriented Control (FOC) VSCF Electric Machines, for the following reasons: 1) Wound-Rotor Doubly-fed electric machine with BMSCC (or RTEC) makes the wound-rotor an active winding set and as a result, does not utilize a wound “field” or field winding; 2) BMSCC (or RTEC) performs natural AC-to-speed-synchronized-variable-AC conversion (i.e., self-commutation) without a DC (low frequency) link stage and without a speed-variant to speed-invariant translation and frequency synthesis process, which distinguish BMSCC from derivatives of FOC; 3) BMSCC (or RTEC) is brushless; 4) BMSCC (or RTEC) is ideal for controlling PF correction and torque control under variable speed conditions; and 5) BMSCC (or RTEC) is compatible with any type or category of electric machine, such as the Brushless Wound-Rotor [Synchronous] Doubly-Fed Electric Machine, which has additional attributes, such as low cost electronics and high efficiency.

Wind Turbines are finding ocean based installations more common for many reasons. Ocean based wind turbines require more durable generators, such as brushless generators incorporating BMSCC. Another advantage of BMSCC is a huge ionic source (the salt brine water of an ocean) for energy storage in the form a salt water chemical battery.

It should now become apparent that any VSCF Wind (or any Renewable Energy Prime Mover) Turbine with “Brushless Multiphase Self-Commutation Control” or BMSCC (or RTEC), such as the Brushless Wound-Rotor [Synchronous] Doubly-Fed Electric Machine, is virtually unknown to electric machine experts or engineers and is very different from all other electric machine technology, including the previous patented technology of this inventor. It should also be understood, that a wind turbine (or any renewable energy prime mover energy converter) requires other important considerations or basic components, such as brake, yawl and pitch control, a tower or other structure, etc., for practical operation and should be included in this invention.

Enhanced Transmission Means (ETM) Invention: See Wind Turbine with Enhanced Transmission Means block 42 of the BMSCC Independent Inventions 45 of FIG. 6. Another important ingredient to wind generation is the transmission. The transmission is a means of increasing the rotational speed of a slow turning windmill (i.e., <100 rpm) to a rotational speed that is more compatible with electric machines (i.e., >900 rpm), such as BMSCC (or RTEC) electric machines, and transferring the tremendous power to the electric machine generator. Reducing the weight and cost of the transmission, while increasing its reliability, are a constant goal. This invention considers an internal gear (or stages of internal gears) with a large ring gear driving smaller pinion gears, which in turn may drive additional stages of transmissions for additional torque ratio change, which in turn drive one or more BMSCC (or RTEC) Electric Machines, as an embodiment of ETM. In addition, this invention considers a flexible torque belt (i.e., timing belt, belts, cables, chain, etc.) or Flexible Transmission Means, which includes a large pulley driving smaller pulleys, which in turn may drive additional stages of transmissions for additional torque ratio change, which in turn drive one or more Electric Machines of any type, as an embodiment of ETM. Further, this invention considers a direct drive (i.e., without transmission) to a single BMSCC (or RTEC) Electric Machine with the possibility of Pole-Pair Emulation, large pole count, or transverse flux configuration as an embodiment of ETM. The Enhance Transmission Means driving electric machines, including BMSCC electric machines, should be useful for other energy converting devise as well.

As used herein, a pulley is a device in a flexible belt transmission system for transferring motion power. For instance, a timing belt pulley has striations on the race face and perpendicular to its race, which mates to the timing belt and provides a locking mechanism for the flexible belt, such as found between a chain and sprocket. As used herein, a timing belt pulley is tantamount to a pulley. In the classic sense, a pulley incorporates a channel for the race that provides friction to a belt.

FIG. 12 shows one embodiment of a transmission mated to at least one Electric Machine System, (preferably a BMSCC (or RTEC) Electric Machine System) employed in a VSCF Wind Turbine. This embodiment employs Friction Belts, Timing Belts, Chains, Cables, or similar Flexible Transmission Means (FTM) If for propagating rotational power from the shaft 2 f of the Wind Turbine Propeller to one or more Electric Machines 3 f (preferably BMSCC Electric Machines). Although FIG. 12 shows four Electric Machines, one or any number of Electric Machines could be incorporated to distribute the stress over multiple units. The combined rated power of each Electric Machine is the total power expected from the Wind Turbine shaft 2 f. Transmission of power is through an arrangement of Pulleys. Since the principle is to increase the speed of the Wind Turbine shaft 2 f to a compatible speed for the Electric Machine shaft pulley 3 f, a Large Pulley 5 f is attached to the wind turbine shaft and a Small Pulley 6 f is attached to the Electric Machine(s). The Flexible Transmission Means follows the circumference speed of the Large Pulley 5 f and propagates that speed to the circumference speed of the Small Pulleys 6 f. The ratio between the circumference of the Large Pulley 5 f, which is attached to the shaft of the Wind Turbine Propeller, and the Small Pulley 6 f, which is attached to the shaft of the Electric Machine, determines the rotational speed increase. Since power is the product of torque and speed, the torque will equally decrease with an increase of speed (or visa-versa). The revolutions-per-minute (RPM) ratio increase is equal to the diameter of large pulley divided by diameter of small pulley. The torque ratio decreases and is the inverse of the speed ratio increase. The Idler Wheels 4 f guide the flexible transmission means 1 f about the Pulleys 5 f & 6 f by applying proper tension on the flexible transmission means or by providing a low loss mechanical channel to the Flexible Transmission Means. FIG. 12 shows one arrangement of Idler Wheels but the number and arrangement of Idler Wheels is dependent on the configuration requirements. The rotation direction of the Wind Mill shaft 10 f would propagate the force 11 f onto the Flexible Transmission Means (FTM).

Two other arrangements of flexible transmission, which would substitute the view 7 f (or similar view) with view 9 f or 8 f. View 9 f shows the Flexible Transmission Means to wrap around the shaft or pulley of the Electric Machine (preferably a BMSCC (or RTEC) Electric Machine System). This View 9 f is flexible transmission arrangement that reverses the direction of the Electric Machine shaft with regard to the Wind Mill shaft. View 8 f shows another stage of speed increase. The shaft 12 f, which operates at the speed from the first flexible transmission means, drives another large pulley 14 f, which drives a second flexible transmission means 13 f, which in turns, drives the shaft of Electric Machine 3 f again with an additional multiplication of speed based on the ratio between the diameter of the pulley 14 f divided by the diameter of the electric machine pulley.

With the many flexible transmission technology commercially available, the preferred flexible transmission means would be a Timing Belt (i.e., Gilmer Belt). Timing Belts are efficient, flexible for smooth torque transfer, quiet, require no lubrication, and are light weight and are striated for absolute tracking with a striated pulley counter-part. Further, the large pulley (gear) 5 f can be made of aluminum or composites for reduced cost or weight because mechanical tolerances are not as critical for flexible transmission belts. Further, the flexible transmission means absorbs stress impulses. The torque rating of the flexible belt is determined by many ingredients, such as belt construction, incorporated material, number of belts, belt dimensions, etc.

Ideally, the flexible transmission (i.e., the Timing Belt, etc.) would be designed and constructed for lifetime service but in practice, this may not be a reality. A monitoring mechanism could sense the condition of the belt or timeout on predicted life expectance of the flexible belt, for automatic replacement, such as by a robotic means that would be evident to a mechanical expert, from a rack of new belts held in storage local to the Flexible Transmission Means for this very purpose. For instance, at a predefined time of life, which is also convenient for overhaul, the wind turbine could be stopped, the idler pulleys de-tensioned, the old belt automatically removed (perhaps by first cutting the belt), a new belt installed, the idler pulleys returned to proper tension, and finally, the wind turbine returned to operation. It is quite practical to perform this operation without stopping the wind turbine.

FIG. 13 shows another embodiment of a transmission mated to at least one Electric Machine Systems and is specific to BMSCC electric machines for VSCF Wind Turbines. This embodiment employs an internal gear (or planetary gear) means for propagating rotational power from the shaft 2 g of the Wind Turbine Propeller to at least one BMSCC (or RTEC) Electric Machines 3 g. Although FIG. 13 shows four BMSCC (or RTEC) Electric Machines, one or any number of BMSCC (or RTEC) Electric Machines could be incorporated. The combined rated power of each BMSCC (or RTEC) Electric Machine is the total power expected from the propeller shaft of the wind turbine. The large ring gear 5 g is attached to the shaft 2 g of the wind mill. The pinion gears 6 g, which are gear driven by said ring gear, is attached to the shaft of the BMSCC (or RTEC) Electric Machine 3 g. The speed ratio and torque ratio of the transmission follows the same relation discussed for the Flexible Transmission Means (FTM).

The Flexible Transmission Means, FIG. 12, showed a transmission embodiment with additional speed increase stages 8 f. The same principle applies to the Internal (or Planetary) Transmission Embodiment.

Regardless of the transmission means, such as flexible or internal, any auxiliary transmission stages for additional speed reduction or speed increase can be based on the flexible transmission means, the internal transmission means, or other transmission means. Further, the exception control resolution of BMSCC could be programmed to reduce stress on the ETM.

There is always the option of attaching a BMSCC electric machine of high pole-pair count directly to the shaft and avoid any ETM. Large pole count means large diameter electric machine frames, which introduce its own set of problems. Perhaps the tradeoff is a limited speed ratio ETM with larger diameter (i.e., large pole count) electric machine generators.

Electric Vehicle (EV) Invention: In general, the introduction of Electric Vehicles (EV) is sure way of saving global energy with efficiency standards. Since electric vehicles contain a means to produce high frequency AC for electric propulsion from a portable storage source, a fleet of electric vehicles become a convenient medium for distributed storage for improving the quality and efficiency of the utility power distribution system. The electric machine of the electric vehicle, which is for motoring during forced acceleration or generating during forced deceleration, and the energy storage source, which is for portable electrical power, are the two distinguishing components of any electric vehicle.

This electric vehicle invention shows three new art: 1) an EV power train with BMSCC means controlling any electric machine (See EV Power Train with RTEC or BMSCC 38 of the BMSCC Dependent Inventions 44 of FIG. 6.); 2) a multiphase high frequency distribution bus means for powering all components in the EV, including the electric machines of the vehicle (See EV Power Train with High Frequency Power Distribution Means (HFPDM) block 40 of the BMSCC Independent Inventions 45 of FIG. 6.), and 3) a power steering assist means (See EV Dual Electric Machine Power Steering Assistance (DEMPSA) block 41 of the BMSCC Independent Inventions 45 of FIG. 6.).

FIG. 14 shows the major components for an electric vehicle power train. People with ordinary skill in the art would understand the components of an electric vehicle and power train. For simplicity, FIG. 14 does not show the undercarriage, suspension, etc. The front power train of the vehicle includes independent left 1 h and right electric machines 2 h, which are preferably BMSCC (or RTEC) electric machines, front articulated axles 7 h with velocity joints 6 h (or universal joints), wheel knuckles 8 h connected to tie rods 9 h and a rack and pinion steering mechanism with steering wheel and shaft 10 h. The rack and pinion steering mechanism for this example may be any steering mechanism with or without power assist. The rear power train of the vehicle may include the same basic mechanism found in the front drive train, including the left side 3 h and right side 4 h electric machines connected to the wheels with articulated axles, which could be BMSCC (or RTEC) electric machines, and the steering mechanism for complete four-wheel steering.

Electric Vehicle (EV) Assistive Steering Invention: See EV Dual Electric Machine Power Steering Assistance (DEMPSA) block 41 of the BMSCC Independent Inventions 45 of FIG. 6. Power assist for EV is achieved by individually adjusting the torque of the right and left independent electric machines for the desired steering response via the appropriate feedback control sensing means, which may even include microprocessors and accelerometers. The manual steering mechanism may be incorporated for failsafe operation and steering integrity during electrical power failure or interruption. Likewise, torque control, stability control, anti-lock braking (ABS), etc. are easily incorporate through independent control of the two separate electric machines and a feedback control mechanism. The rear power train may include two electric machines, as shown in FIG. 14. When incorporating two electric machines certain benefits result, such as no differential requirement, stability control, ABS, etc., which are easily facilitated by independent control of the two separate electric machines and the appropriate feedback control mechanism. Further, the same power steering assistance described for the front power train may be incorporated in the rear power train for complete four-wheel steering with the appropriate feedback mechanism.

Electric Vehicle (EV) Power Distribution Bus System Invention: See EV Power Train with High Frequency Power Distribution Means (HFPDM) block 40 of the BMSCC Independent Inventions 45 of FIG. 6. The EV Power Distribution Bus would include any energy storage device, such as battery packs, fuel cells, etc., or any portable electric source, such as an electric generator driven by a prime mover (i.e., internal combustion engine, turbine, etc.) 12 h. It also includes a high power electrical bus 14 h, which distributes power to all electric machines and other electrical components of the electric vehicle. The Electrical Bus Control Unit 13 h at the very least monitors the high power bus and maintains electrical integrity. More likely, the Electrical Bus Control Unit 13 h converts the electrical power from the power sources 12 h, which may be pure DC, to the Power Distribution Medium 14 h, which may be pure DC, high frequency AC with a DC envelop, multiphase high frequency AC with DC envelops, or high frequency AC with multiphase AC envelops. The high power bus control unit 13 h could be a BMSCC Stationary or Rotary Phase or Frequency Converter, which can easily convert any DC or AC source 12 h to a multiple phase high frequency AC Power Distribution Bus simply by not incorporating the secondary side of synchronous modems of the BMSCC control unit. If the BMSCC control unit included the secondary side of the synchronous modems, a multiple phase Low Frequency AC Power Distribution Bus would be realized.

A high frequency, high power AC distribution system has added protection capability and advantages. For instance, the high power bus control unit 13 h will monitor the current at the high frequency for any alarm condition, such as a short circuit condition, and shut off disconnect the source 12 h within the expected half cycle period of the high frequency AC or at the next zero crossing of the AC power, which always occurs at the high frequency. Since power for a high frequency high power bus is applied on a half cycle basis, a short circuit alarm could stop the switching within half cycle, which is well within the intense pulse current duration immunity tolerance of most power semiconductors. A high frequency distribution bus allows for simple, compact step-up or step-down voltage conversion at any point along the bus. A high frequency distribution bus allows for failsafe operation with continued operation with any remaining phases of integrity with phase failures. A high frequency multiphase distribution bus allows for distributing the total power over as many wires and connections as phases, which improves electrical efficiency. A high frequency multiphase distribution bus easily accommodates the installation of BMSCC wound-rotor doubly-fed electric machines. A multiple phase high frequency bus may require special accommodations for practical high frequency operation, such as Litz wire, etc.

EV with BMSCC or RTEC Electric Machines: See EV Power Train with RTEC or BMSCC 38 of the BMSCC Dependent Inventions 44 of FIG. 6. BMSCC electric machines have many advantages in an electric vehicle application. If compared to a the most commonly installed EV electric machine, any category of singly-fed electric machine, a BMSCC Wound-Rotor Doubly-Fed Electric Machine shows certain benefits. A BMSCC Wound-Rotor Doubly-Fed (WRDF) Electric Machine operates at 7200 rpm@1 pole-pair with 60 Hz (from the high power distribution bus), which is twice the speed and half the size of a comparably sized singly-fed electric machine. At full excitation frequency (or speed), the BMSCC-WRDF electric machine operates at half the voltage and with lower eddy current losses. As a fully symmetrical electric machine, a BMSCC-WRDF electric machine can motor or generator without additional electronic support. Any singly-fed or doubly-fed electric machine with BMSCC shows transfer of power to or from the storage power source 12 h with evenly distributed waveforms of low harmonic content and without additional stages of electronic conditioning.

Incorporating multiple BMSCC (or RTEC) electric machines would conveniently benefit with a high power electrical bus 14 h operating with high frequency AC with a DC envelop, multiphase high frequency AC with DC envelops, or high frequency AC with multiphase AC envelops. For instance, a high frequency, high power distribution system connects directly to the primary side of the PDF-HFT or PDF-HFT-PIF-HFT of the BMSCC (or RTEC) electric machines and avoids the primary side synchronous modem stage, since the primary synchronous modem for all electric machines along the distribution bus is the high power bus control unit 13 h that is without the secondary synchronous modem. The Bus Control Unit 13 h becomes an integral part of any BMSCC art employed in the EV. In this configuration, it will be understood frequency bus 14 h, the high power bus control unit 13 h, and the partial BMSCC electric machine, as described, is a complete BMSCC electric machine with said components distributed over a greater distance. 

1. A Brushless Multiphase Self-Commutation Controller (or BMSCC) or Real Time Emulation Controller (or RTEC) for adjusting or re-fabricating low frequency “input signal waveforms” into low frequency, position and speed synchronized “output signal waveforms” for completing the excitation and control of electric apparatus, such as excitation control of the moving or stationary active winding sets of electric machines, comprising: at least one Position Dependent Flux High Frequency Transformer (or PDF-HFT) means with at least one high frequency phase winding on the primary side of said PDF-HFT or “primary phase windings” inductively coupled to at least one high frequency phase winding on the secondary side of said PDF-HFT or “secondary phase windings” by common magnetic paths linking said primary and said secondary sides or “mutual magnetic paths”; wherein said high frequency is of higher frequency than said low frequency; wherein said high frequency electrical signal waveforms at the terminals of said primary phase windings or “first signal waveforms” are amplified to other high frequency signal waveforms at the terminals of said secondary phase windings or “second signal waveforms” in accordance to the ratio of winding-turns between said primary phase windings and said secondary phase windings; wherein relative variation between said primary phase windings and said secondary phase windings selected from a group consisting of movement, speed, angular position, angular velocity, placement, position, distance, reluctance, and phase angle changes said mutual magnetic path; whereby said first signal waveforms are converted to said second signal waveforms by inducing said relative variation as additional waveform components onto the modulation envelops of said second signal waveforms with said winding-turns ratio of amplification; at least one Position Independent High Frequency Transformer (PIF-HFT) means with equal number of phase windings stationed on the primary side and on the secondary side: wherein common magnetic paths mutually couple said phase windings of like phase on said primary and secondary sides; wherein common magnetic paths that mutually couple said phase windings of unlike phases are mitigated; wherein any movement or change in position between said primary side and said secondary side of said PIF-HFT does not change the common magnetic path linking said primary and secondary phase windings; whereby any electrical signal waveform on said primary phase windings is induced on said secondary phase windings of like phase of said PIF-HFT with little waveform component change as a result of speed or position of said movement but with an amplification in accordance to the ratio of winding-turns between said primary phase windings and said secondary phase windings; wherein the terminals of said secondary phase windings of said PIF-HFT connect directly to the terminals of said secondary phase windings of said PDF-HFT with like phase: wherein said secondary windings of said PDF-HFT are stationary relative to said secondary windings of said PIF-HFT; whereby said secondary phase signal waveforms of said PDF-HFT become said primary phase signal waveforms of said PIF-HFT of like phase but with an amplification in accordance to the ratio of winding-turns between said primary phase windings and said secondary phase windings of said PIF-HFT; whereby said PDF-HFT and said PIF-HFT become a PDF-HFT+PIF-HFT Combination; whereby the primary side of said PDF-HFT+PIF-HFT Combination is selected from a group consisting of said primary side of said PDF-HFT and said primary side of said PIF-HFT and the secondary side of said PDF-HFT+PIF-HFT Combination is selected from a group consisting of said primary side of said PIF-HFT and the primary side of said PDF-HFT not selected as the primary side of said PDF-HFT+PIF-HFT Combination; Section Pages: 2-12 Document Pages: 126-136 whereby the moving side of said PDF-HFT+PIF-HFT Combination is considered said secondary side of said PDF-HFT and said secondary side of said of said PIF-HFT; at least one Magnetizing Current Generator means (or MCG) for first applying high frequency oscillating Magneto-Motive-Forces (or MMF) to the terminals of said phase windings of said PDF-HFT+PIF-HFT Combination by gating electrical power from said input signal waveform to at least one of said phase windings; whereby unbiased high frequency oscillating magnetic fields are first established in the core of said PDF-HFT+PIF-HFT Combination; wherein said gating of electrical power comprises power switching means selected from a group consisting of electric, electronic, and electromechanical circuits and components; whereby said first signal waveforms are unbiased high frequency waveforms with modulation envelops in accordance to said input signal waveforms; whereby said second signal waveforms are first unbiased high frequency waveforms with modulation envelops in accordance to said output signal waveforms, said variation, and said winding-turns ratio amplification; at least one Modulating and Demodulating (or MODEM) means for coupling between low-to-high frequency signal waveforms selected from a group consisting of said input signal waveforms to said first signal waveforms or “Primary MODEM” and said output signal waveforms to said second signal waveforms or “Secondary MODEM”: wherein said coupling means of said MODEM means gates electrical power between said low-to-high frequency signal waveforms in synchronous relationship to at least one measurable derivative of said unbiased high frequency oscillating magnetic fields as provided by said MCG for providing “compensated gating”; wherein said electrical power and said low-to-high frequency signal waveforms on said phase windings of said PDF-HFT+PIF-HFT Combination are re-fabricated by dynamically changing the relative timing of said compensated gating for providing Section Pages: 3-12 Document Pages: 127-136 “compensated gating dynamics”; wherein said gating of electrical power comprises power switching means selected from a group consisting of electric, electronic, and electromechanical circuits and components.
 2. A combination defined in claim 1 further comprising environmental stress immunity means: whereby said BMSCC experiences similar environmental stress as said electric apparatus because of the symbiotic proximity of BMSCC to said electric apparatus; wherein stress on sensitive electronic, electrical, mechanical components and assemblies due to local operating conditions of said electric apparatus are mitigated;
 3. A combination defined in claim 2 wherein said Environmental Stress Immunity Means further comprises art selected from a group consisting of up-to-date science and new science further selected from a group consisting of design, construction, manufacturing, modification, materials, physics, and conditioning of said sensitive components and assemblies for mitigating said environmental stress.
 4. A combination defined in claim 2 wherein said environmental stress immunity means are selected from a group consisting of passive and active means of heat convection, heat conduction, vaporization, and heat radiation to remove heat from said sensitive components and assemblies;
 5. A combination defined in claim 2 wherein said environmental stress immunity means are selected from a group consisting of potting and mounting techniques of said sensitive components and assemblies.
 6. A combination defined in claim 2 wherein said environmental stress immunity means further comprise installing said sensitive components and assemblies that are rated for operation at temperatures greater than 49 degrees Celsius.
 7. A combination defined in claim 2 wherein said environmental stress immunity means further comprise installing said sensitive components and assemblies that are rated at mechanical acceleration levels greater than or equal to one unit of gravity.
 8. A combination defined in claim 1 further comprising a magnetic core composed of material for supporting said mutual magnetic path of said primary side and said secondary side of said PDF-HFT+PIF-HFT Combination selected from a group consisting of ribbons, tapes, laminations, powders further selected from a group consisting of amorphous metals, nanotechnology metals, powdered metals, and low loss metals.
 9. A combination defined in claim 1 further comprising at least one air-gap between said primary side and said secondary side of said PDF-HFT+PIF-HFT Combination for providing features selected from a group consisting of non-obstructive movement between said primary and secondary sides and improved Flux Density distribution;
 10. A combination defined in claim 1 wherein said phase windings on at least one side of said PDF-HFT of said PDF-HFT+PIF-HFT Combination are balanced multiple phase windings; wherein each phase winding of said balanced multiple phase windings are evenly distributed along a plane that is perpendicular to said magnetic path in accordance to relative angles between phases of said balanced multiphase; wherein the balanced multiple phase windings evenly overlap the same area on said plane in accordance to relative angles between phases of said balanced multiphase; whereby movement between primary and secondary sides of said PDF-HFT changes dimensions of said magnetic path passing through said phase windings.
 11. A combination defined in claim 1 wherein the number of said phase windings on said primary side of said PDF-HFT+PIF-HFT Combination corresponds to at least the number of phase signals of said input signal waveforms and the number of said phase windings on said secondary side of said PDF-HFT+PIF-HFT Combination corresponds to at least the number of phase signals of said output signal waveforms.
 12. A combination defined in claim 1 wherein said PDF-HFT+PIF-HFT Combination comprises a form-factor selected from a group consisting of rotating form-factor, linear form-factor, axial flux form-factor, radial flux form-factor, transverse flux form-factor, and multiple air-gap form-factor.
 13. A combination defined in claim 1, wherein said winding-turns ratio of said PDF-HFT+PIF-HFT Combination is selected from a group consisting of step-up, step-down, and neutral ratios.
 14. A combination defined in claim 1, wherein said input signal waveforms are selected from a group consisting of Direct Current (DC) signals and Alternating Current (AC) signals with at least one phase further selected from a group consisting of fix frequency and variable frequency.
 15. A combination defined in claim 1, wherein said PDF-HFT+PIF-HFT Combination further comprises a transformer means for coupling signals selected from a group consisting of logic signals and logic power;
 16. A combination defined in claim 1, wherein said synchronous relationship for providing said compensated gating is established by at least one Synchronizing Means (SM) comprising a phase lock loop (PLL) means.
 17. A combination defined in claim 1, wherein said synchronous relationship for providing said compensated gating is established by at least one Synchronizing Means (SM) comprising a synchronizing reference means provided by a communication interface.
 18. A combination defined in claim 1, wherein at least one of said MODEM means can be remotely situated at a distance from said PDF-HFT+PIF-HFT Combination; whereby a high frequency multiphase distribution bus for carrying said first signal waveforms of said distance exists between said remotely placed MODEM means and said terminals of said primary phase windings of said PDF-HFT+PIF-HFT Combination.
 19. A combination defined in claim 1, wherein said BMSCC comprises art selected from a group consisting of up-to-date science and new science further selected from a group consisting of winding arrangements, circuits, environmental stress reducing techniques, manufacturing techniques, construction techniques, electrical components, electronic components, nanotechnology, and materials.
 20. A combination defined in claim 1, further comprising at least one said Magnetizing Current Generator (or MCG) means for at least one of said windings of said PDF-HFT+PIF-HFT Combination.
 21. A combination defined in claim 1, wherein at least one said Magnetizing Current Generator (or MCG) means dynamically changes the waveform characteristics of said high frequency oscillating magnetic field on an untimely basis (i.e., at any time).
 22. A combination defined in claim 1, wherein at least one said Magnetizing Current Generator (or MCG) means is functionally integrated into at least one of said MODEM means; whereby said MCG means and said MODEM means are integral functions.
 23. A combination defined in claim 1, further comprising at least one said MODEM means for at least one of said phase windings of said PDF-HFT+PIF-HFT Combination.
 24. A combination defined in claim 23, wherein at least one said MODEM means provides said compensated gating dynamics independently from other said MODEM means.
 25. A combination defined in claim 1, wherein said compensated gating dynamics of at least one of said MODEM means are adjusted for sharing said oscillating magnetic field energy between said phase windings of said PDF-HFT+PIF-HFT Combination; wherein said adjustment can be performed on an untimely basis (i.e., at any time); whereby said low frequency signal waveforms are re-fabricated in accordance with said sharing as provided by said compensated gating dynamics.
 26. A combination defined in claim 25, wherein said BMSCC is without movement; providing at least a converter means selected from a group consisting of Stationary Phase Converters and Stationary Frequency Converter means.
 27. A combination defined in claim 1, wherein said compensated gating dynamics of at least one of said MODEM means are changed on an untimely basis (i.e., at any time).
 28. A combination defined in claim 1, further comprising resonant switching: wherein said gating selected from a group consisting of said compensated gating dynamics of at least one of said MODEM means and said gating electrical power of at least one of said MCG means comprises resonant switching.
 29. A combination defined in claim 28, wherein said resonant switching further comprise iterative averaging to compensate for any circuit delays for predictable zero crossing for providing Soft Switching Compensation (SSC).
 30. A combination defined in claim 1, wherein said compensated gating dynamics of at least one of said MODEM means comprises Compensated Transition Offset Modulation (CTOM) for re-fabrication of waveforms selected from a group consisting of said low frequency signal waveforms and said high frequency signal waveforms: wherein said compensated gating dynamics comprises dynamically adjusting the timing of said gating relative to said synchronous reference; wherein said adjustment can be performed on an untimely basis (i.e., at any time).
 31. A combination defined in claim 1, wherein said compensated gating dynamics of at least one of said MODEM means comprises Compensated Pulse Density Modulation (CPDM) for re-fabrication of waveforms selected from a group consisting of said low frequency signal waveforms and said high frequency signal waveforms: wherein said compensated gating dynamics continue for a burst of half-cycles of said unbiased high frequency waveform or “string”; wherein the number of said half-cycles contained in said string or “string density” determines Amount of electrical energy contained in said string; wherein said string density of said string is selected from a group consisting of no half-cycles and at least one half-cycle; wherein said string density can change on an untimely basis (i.e., at any time); wherein each said string occurs on intervals of more than one half-cycle or “frame”; wherein the number of half-cycles per said frame is greater than said string density; wherein the number of half-cycles per said frame can change on an untimely basis (i.e., at any time); wherein said frame between said MODEM means on said primary side of said PDF-HFT+PIF-HFT Combination or “first MODEM means” and said MODEM means on said secondary side of said PDF-HFT+PIF-HFT Combination or “second MODEM means” are skewed a number of said half-cycles selected from a group consisting of no half-cycles and at least one half-cycle; wherein said string density may be different between said first MODEM means and said second MODEM means by a number of said half-cycles selected from a group consisting of no half-cycles and at least one half-cycle.
 32. A combination defined in claim 1, wherein said compensated gating dynamics of at least one of said MODEM means are selected from a group consisting of Compensated Transition Offset Modulation (CTOM) and Compensated Pulse Density Modulation (CPDM).
 33. A combination defined in claim 9, wherein the stator body of said PDF-HFT+PIF-HFT Combination can be mechanically moved relative to any stationary reference of said PDF-HFT+PIF-HFT Combination simultaneously with said compensated gating dynamics for additional adjustment or re-fabrication of said first or second signal waveforms.
 34. A combination defined in claim 33, wherein said means for providing said mechanical movement are selected from a group consisting of manual systems, electric motor systems, electric servo systems, electric Synchro-Resolver systems, constant ratio transmission systems, and variable ratio transmissions systems.
 35. A combination defined in claim 1, wherein a first event establishes the magnetizing current levels or MMF within said phase windings of said PDF-HFT by said MCG; wherein a second event establishes the method of operation and control selected from a group consisting of Compensated Transition Offset Modulation (CTOM) and Compensated Pulse Density Modulation (CPDM); wherein said second event occurs after said first event.
 36. A combination defined in claim 35, wherein said method of operation and control comprises the Basic Three Step Process Control Means (BTPCM) of BMSCC that further comprises the steps of: a) capture data selected from a group consisting of operating parameters and commands further selected from a group consisting of remote data and local data; b) determine adjustments for said compensated gating dynamics as selected from a group consisting of calculations and communications based on said captured data; c) control said compensated gating dynamics in accordance to said adjustments; d) repeat the method from (a).
 37. A combination defined in claim 36, wherein said PDF-HFT additionally functions as a speed-position resolver means (SPRM) for sensing information selected from a group consisting of said speed and said position.
 38. A combination defined in claim 36, wherein any Capture, Control, Command, and Communication (CCCC) means of said Basic Three Step Process Control Means (BTPCM) further comprises components selected from a group consisting of analog processors and digital processors further selected from a group consisting of hardware and software control.
 39. A combination defined in claim 1 wherein the moving body of said BMSCC is mechanically moved by means selected from a group consisting of electric motors, electronically controlled electric motors, synchros, servos, mechanical transmission means, and the intrinsic electric motor properties of said BSMCC; wherein said transmission means is selected from a group further consisting of gears, pulleys, sprockets, chains, and belts; providing at least a Rotary Phase Converter or Rotary Frequency Converter means.
 40. A gadget as in claim 1, wherein there is an arrangement of at least two BMSCC without Secondary MODEM; wherein each of said BMSCC is remotely situated at a distance; wherein a high frequency distribution bus of said distance exists between each of said BMSCC; wherein said high frequency distribution bus is selected from a group consisting of single phase AC and multiple phase AC; wherein said high frequency distribution bus is connected phase to phase to at least two high frequency transformers selected from a group consisting of said PDF-HFT, PIF HFT and said PDF-HFT+PIF HFT Combination of said BMSCC; whereby said high frequency distribution bus can be tapped for electrical power at least at one location along said distance of said bus.
 41. A singly-fed or doubly-fed Electric Machine System as defined in claim 1, wherein said secondary phase windings of said BMSCC excites the stationary (or stator) phase windings of an electric machine selected from a group consisting of axial flux, radial flux, transverse flux, rotating and linear moving Wound-Rotor Doubly-Fed Electric Machines (WRDFEM), Asynchronous Electric Machines (AEM), Synchronous Electric Machines (SEM) with permanent magnets, Synchronous Electric Machines (SEM) with field wound electromagnets, and Reluctance Electric Machines (REM); wherein said secondary phase windings of said BMSCC are connected to said stationary (or stator) phase windings of said electric machine; wherein said moving side of said PDF-HFT+PIF-HFT Combination of said BMSCC moves at the same speed or placement as the moving body of said electric machine. 